CN102468764A

CN102468764A - Adjusting gain method of resonant converter and apparatus thereof

Info

Publication number: CN102468764A
Application number: CN2010105383168A
Authority: CN
Inventors: 吴洪洋; 王彬; 言超
Original assignee: Delta Optoelectronics Inc
Current assignee: Delta Optoelectronics Inc
Priority date: 2010-11-01
Filing date: 2010-11-01
Publication date: 2012-05-23
Anticipated expiration: 2030-11-01
Also published as: CN102468764B

Abstract

The invention provides an adjusting gain apparatus of a resonant converter and a method thereof. The apparatus and the method are used to adjust and control a direct current gain of the resonant converter so as to improve power supply usage performance of a circuit. In the invention, a phase shift module is assembled on the resonant converter and is used to generate a first control signal which controls the main driver of the resonant converter and generate a second control signal which controls the secondary driver of the resonant converter. The first control signal and the second control signal possess a phase shift which is used to control the direct current gain of the resonant converter. According to the invention, through adjusting and controlling the direct current gain of the resonant converter, the direct current gain can be in an optimized state, a power supply usage efficiency can be increased and the usage performance of the power supply can be improved.

Description

The adjusting gain method and the device thereof of resonant mode transducer

Technical field

The present invention relates to a kind of adjusting gain method and device thereof, relate in particular to a kind of adjusting gain method and device thereof that is applied to the resonant mode transducer.

Background technology

Effectively the controlling and using of power supply when exploitation consumption-orientation and industrial electronics, is a main emphasis of considering.And the wherein a kind of pattern that is used for power conversion system now is resonant mode transducer (resonant converter), and it includes inductor-capacitor (L-C) network of various configurations, in order to mould the waveform of the curtage of given switch element in the whole circuit.Various electronic component can be used to design a resonant mode transducer, and synchronous rectifier (synchronous rectifiers SRs) then often is used to need alternating current (AC) is transferred in the application of direct current (DC).Synchronous rectifier includes a diode and a transistor (being typically a mos field effect transistor MOSFET) that is connected in parallel.When operational applications, when this diode is in a forward bias, then this transistor can be activated to lower pressure drop, so as to reducing loss in the circuit.

Under practical working situation; No matter whether use synchronous rectifier, this resonant mode transducer all can meet with a problem, promptly in the scope of this transducer operate as normal; Its DC current gain (nVo/Vin) changes for nonmonotonicity, and a plurality of operating frequencies possibly appear in promptly corresponding same gain.Moreover in any case change the frequency of resonant mode transducer, its DC current gain all can't be the null value or the null value that levels off to.This will reduce the usefulness of resonant mode transducer 101 as the power controling machine system in electronic application or the consumer device, and this usefulness refers to obtain according to frequency the gain reaction of a stable and monotonicity (like linearity), to avoid the element infringement; And produce one zero DC current gains, to obtain a smooth-going starting waveform by a no-voltage or the no-voltage that levels off to.

Figure 1A-Fig. 1 C discloses the graph of a relation between its switching frequency and DC current gain when the resonant mode transducer is in its normal range of operation.It should be noted that for typical resonance formula converter application (like LLC resonant mode transducer) being difficult to only depend on increases switching frequency and reduce its DC current gain to one null value, to reach the requirement that starts from no-voltage smooth-goingly.For instance; Figure 1A has disclosed underload and both typical DC current gain curves of heavy duty; The x axle is represented the normalizing operation frequency of circuit; Be the ratio of the characteristic resonant frequency of frequency of operation and this resonant circuit, the y axle is represented the DC current gain level, takes advantage of the ratio of n (turn ratio of transformer T) and this input voltage vin for output voltage V o.For light load operation, in same frequency range, its DC current gain curve 1001 is higher than heavy duty person's curve 1003.Along with the increase of switching frequency, this underloaded gain is all greater than a particular value, shown in Figure 1A 0.7.Constantly increase frequency to higher value and can significantly not reduce the net value of DC current gain more not to the utmost, and can increase the loss of circuit element and cause circuit to damage (, burning out etc.) as overheated.

Figure 1B is the circuit diagram according to an example embodiment, and it shows the tool one or the resonant mode transducer of multiparasitization electric capacity more.In the present embodiment, the situation of parasitic capacitance Cp and Cs resonant network and the rectifier network circuit during with the reflection real work that imported this resonant mode converter circuit system respectively.Usually, electronic component all contains certain parasitic parameter, like parasitic capacitance, inductance or resistance etc.The coil of transformer or switch element all include parasitic capacitance.Situation when therefore capacitor C P 1005 and CS 1007 can be added in this transducer with the real work of reflection circuit.

Unfortunately, when light load operation, electric capacity can cause the charge pump effect and increase DC current gain.This phenomenon is illustrated in Fig. 1 C, and it discloses example embodiment of the present invention in the resonant mode transducer that the adds capacity cell DC current gain curve that both are simulated to underload and heavy duty.The charge pump effect, shown in the curve 1009 among the figure, multipotency is passed to the output of this resonant mode transducer because

electric capacity

1005 and 1007 can make more, and causes output voltage to increase.This phenomenon is more detailed is described in U.S. Patent number the 7th, 733, in 669, all incorporates in this and to consider and examine.

It should be noted that the phenomenon in Fig. 1 C, have same gain level (like gain=A) because the curve 1009 that the existence of this charge pump charge pump effect makes the DC current gain curve 1009a that under the underloading situation, answered monotone variation originally become a non-monotone variation is a corresponding different operating frequency (like frequency f 1 and f2).It is chaotic that circuit control is taken place, and the gain characteristic that can't expect will cause this transducer instability and bear high power supply consume.

The technological deficiency summary of the invention

Restriction and defective in view of known technology; The present invention proposes a kind of " the adjusting gain method and the device thereof of resonant mode transducer "; DC current gain through regulating control resonant mode transducer makes it reach optimization, and then increases the power supply service efficiency, has improved the serviceability of power supply.

This section outline some characteristic of the present invention, other characteristics will be described in follow-up paragraph.The present invention is through additional claim definition, and it is herein incorporated paragraph as a reference.

Main purpose of the present invention is adjusting gain method and the device that a kind of resonant mode transducer is provided; Through regulating the DC current gain of control resonant mode transducer; Make it according to frequency/phase shifting angle or other changes thereby the gain of obtaining a stable and monotonicity (like linearity), and avoid the element infringement; Simultaneously can produce one zero DC current gains, to be obtained a smooth-going starting waveform by a no-voltage, the while can increase the power supply service efficiency.

For reaching above-mentioned purpose, a broad sense execution mode of the present invention is that a kind of adjusting gain method that is applied to the resonant mode transducer is provided, and it comprises step: produce one first control signal, in order to control a main driver of a resonant mode transducer; And produce one second control signal, in order to control a less important driver of this resonant mode transducer, wherein this first control signal and this second control signal have a phase shifting angle, in order to control a DC current gain of this resonant mode transducer.

For reaching above-mentioned purpose, another broad sense execution mode of the present invention is for providing one to regulate gain apparatus, and it comprises: a delay circuit; And a control module, be coupled to this delay circuit, and assembly provides and exports this delay circuit to, produce one first control signal in order to a output voltage and go to control a main driver of this resonant mode transducer according to a resonant mode transducer; And produce one second control signal and go to control a less important driver of this resonant mode transducer; Wherein this first control signal and this second control signal have a phase shifting angle, in order to control a DC current gain of this resonant mode transducer.

For reaching above-mentioned purpose, another broad sense execution mode of the present invention is for providing one to regulate gain apparatus, and it comprises: a resonant mode transducer has a main driver and a less important driver; And a phase shift block, being coupled to this main driver and this less important driver, this phase shift block produces one first control signal with this main driver of control and produce one second control signal to control this less important driver; Wherein this first control signal and this second control signal have a phase shifting angle, in order to control a DC current gain of this resonant mode transducer.

The present invention makes it reach optimization through the DC current gain of regulating control resonant mode transducer, and then increases the power supply service efficiency, has improved the serviceability of power supply.

The present invention must explain through attached drawings and embodiment, makes a clearer understanding.

Description of drawings

Figure 1A to Fig. 1 C: the graph of a relation when it discloses to the resonant mode converter application between its switching frequency and DC current gain;

Fig. 2: its resonant mode converter bank that discloses example embodiment of the present invention is furnished with the block diagram of a phase shift block, in order to regulate the DC current gain of resonant mode transducer;

Fig. 3: it discloses the LLC serial-resonant converter circuit sketch map of example embodiment of the present invention, and it is controlled direct current through switching frequency and increases the electricity gain;

Fig. 4: the time-histories sketch map of the phase shifting angle of the main driver of resonant mode transducer and less important driver in its announcement example embodiment of the present invention;

Fig. 5 A: it discloses the DC current gain curve that example embodiment of the present invention is simulated with the means of compensate for parasitic capacitance;

Fig. 5 B and Fig. 5 C: it discloses the phase shift of resonant mode transducer in the various embodiments of the present invention and the graph of a relation of voltage gain;

Fig. 6 A: resonant mode transducer combo one phase shift block is to regulate the circuit diagram of DC current gain in its announcement example embodiment of the present invention;

Fig. 6 B and Fig. 6 C: it discloses in various embodiments of the present invention with FREQUENCY CONTROL, the Dead Time of phase shift block and regulates control and phase shifting control ability as the application sketch map of control modules individually;

Fig. 6 D: the resonant mode transducer is regulated the circuit diagram of the phase shift block institute assembly of DC current gain with using different error amplifiers in its announcement example embodiment of the present invention;

Fig. 6 E: it discloses the flow chart of regulating resonant mode transducer DC current gain in the example embodiment of the present invention;

Fig. 7 A to Fig. 7 E: it discloses, and the resonant mode transducer is in time according to the behavior timing diagram of phase shifting angle between main and less important driver in the various embodiments of the present invention, and wherein this phase shifting angle surpasses preplanned Dead Time between driver;

Fig. 8 A to Fig. 8 E: the resonant mode transducer is in time according to the main behavior timing diagram that reaches phase shifting angle between less important driver among this each embodiment of its announcement; Wherein should be main and less important driver between phase shifting angle have a preplanned Dead Time, it is less than the phase shift between driver;

Fig. 9: strain stress relation figure is regulated in its phase shift that discloses a resonant mode transducer in the example embodiment of the present invention.

Description of reference numerals in the above-mentioned accompanying drawing is following:

1000,1008: the DC current gain curve chart

1001,1003,1009,1009a: DC current gain curve

1004: circuit diagram

1005,1007: capacity cell

100: resonant mode converter application Circuits System

101: the resonant mode transducer

103: main driver

105: less important driver, synchronous rectifier driver

107: phase shift block

201,203: synchronous rectifier

201a-b, 203a-b: main switch element

205: synchronous rectifier, resonant mode inductor

207: the magnetization load inductance

209: the resonant mode capacitor

211: transformer

213: main coil

215a, 215b: less important coil

217: the rectangular wave input voltage

219: load voltage

225: dotted line

225a: rectangular wave generator

227: dotted line

227a: rectifier network

229: transformer turn ratio

235: resonant network

300: the time-histories sketch map

301: the rectangular wave input

303: the pulse of less important (synchronous rectifier) driver

303a: less important driver pulse

305,307: main driver pulse

410: the DC current gain curve chart

411,413: the DC current gain curve

The 415:x axle

417: block

500: application circuit

501: the resonant mode transducer

503: phase shift block

505: error amplifier

507,509: resistance

511: resonant mode transducer control module

511a: frequency adjustment control input

511b: Dead Time control input

513: switch element

515: load impedance

517: smoothing capacitor

519: compensation output signal

521: delay circuit

523: frequency controller

525: signal generator

527: phase-shift controller

529: frequency is responded curve

531: the phase shift curve

The 533:x axle

535a, 535b: voltage range

537: phase shift block

538: application circuit

539: error amplifier

540: flow process

541: amplifier circuit

543,545,547: step

600,604,610,614,618: circuit diagram

602,606,612,616,620: graph of a relation

603,613,617:ON state

The 607:OFF state

609: rise progressively

700,704,708,712,718: circuit diagram

702,706,710,714,720: graph of a relation

703,707,717:ON state

711: rise progressively

The 715:OFF state

800: chart

801: time of delay

803,807,811: Dead Time

810,820: timing diagram

ASIC: application-specific integrated circuit (ASIC)

Co: smoothing capacitor

Cp: parasitic capacitance

Cr: resonant mode capacitor

Cs: parasitic capacitance

DSP: digital signal processor

EA, EAF: error amplifier

EAD: amplifier circuit

Fea: output signal

Fref: reference voltage

F1, f2: frequency

IQ6, ICo, ILr, IRL: electric current

Lm: magnetization load inductance

Lr: resonant mode inductor

Q1～Q4: switch element

Q5～Q6: synchronous rectifier

Qd: switch

Rd, Rf: resistance

RL: load resistance

Ro: load impedance

RCD: resistor-capacitor diode

VAB: rectangular wave input voltage, supply voltage

Vea: error voltage signal

Vin: supply voltage

VL: load voltage

Vo: output (load) voltage

Vref: reference voltage

VD: supply voltage

S1: first (mainly) control signal

S2: second (less important) control signal

T: transformer

T0～t6: time point

ZVS: efficient ZVT

α: phase shift (delay)

α 1～α 3: phase angle (poor)

Embodiment

Some exemplary embodiments that embody characteristic of the present invention and advantage will be described in detail in the explanation of back segment.Be understood that the present invention can have various variations on different modes, it does not depart from the scope of the present invention, and explanation wherein and accompanying drawing be used as the usefulness of explanation in itself, but not in order to restriction the present invention.

The block diagram that Fig. 2 is furnished with a phase shift block (phase shiftmodule) for the resonant mode converter bank of example embodiment of the present invention is in order to regulate the DC current gain (DC gain) of resonant mode transducer.Resonant mode transducer 101 is a power supply changeover device pattern, is used for needing in circuit, to carry out the electronic equipment that high-effect power supply switches.When being made up of inductor-capacitor (L-C) network of various assembly, resonant mode transducer 101 uses circuit capacitances and inductance to remove to mould whole the be driven in electric current of given switch element or the waveform of voltage, and this switch element can be for like Mosfet, elements such as IGBT.

Synchronous rectifier (SRs) is generally used for efficient operable transducer, like resonant mode transducer 101 grades to reduce the loss in the circuit.Fig. 3 promptly discloses the present invention and is applied to the synchronous rectifier 201 of resonant mode converter circuit system and 203 preferable practicing.

As stated,

synchronous rectifier

201 and 203 includes a diode typically and is connected in parallel to a transistor, promptly like a power metal oxide semiconductor field-effect transistor (power MOSFET).

Shown in each embodiment, resonant mode transducer 101 also comprises one or more main switch element, as 201a-b (Q2, Q3) and 203a-b (Q1, Q4) these switch elements can be MOSFET, BJT or IGBT etc.This main switch element is by 103 drivings of main driver; This synchronous rectifier is then by 105 drivings of less important driver; And 103 of main drivers that drive the less important driver 105 of this synchronous rectifier and drive these resonant mode transducer 101 main switch elements do not have and postpone, make this

synchronous rectifier

201 and 203 with accordingly mainly switch element (as shown in Figure 3, as switch element 201a; During 201b work; Synchronous rectifier 201 work is 201a-201b with synchronous rectifier 201 corresponding elements promptly, in like manner, with synchronous rectifier 203 corresponding elements be 203a-203b) and be activated at one time.

Under this kind control mode, at

synchronous rectifier

201 and 203 before less important driver 105 opens in by circuit, can flow through the earlier body diode of

synchronous rectifier

201 and 203 of electric current.For reduce because of electric current flow through that synchronous rectifiers body diode produces consume;

Synchronous rectifier

201 and 203 can be consumed to lower slightly early than the time of main driver 103 driving respective switch element 201a-b and 203a-b by the time of less important driver 105 startups.So way introduce a phase difference (phase difference) in

synchronous rectifier

201 and 203 and corresponding main switch element 201a-b and 203a-b between.This synchronous rectifier will be activated with the difference of a diode current flow time/phase place (body diode of this synchronous rectifier is prior to the time or the pairing phase place of this section period of the conducting of its corresponding main switch element) early than its corresponding main switch element at present in advance.

The resonant mode converter application Circuits System 100 of Fig. 2 includes a resonant mode transducer 101, and its assembly has a phase shift block 107.As shown in the figure, this phase shift block 107 is electrically connected to the main driver 103 of these resonant mode transducer 101 switch elements and the less important driver 105 of these resonant mode transducer 101 synchronous rectifiers.When operating, this phase shift block 107 can produce a control signal S1, in order to the drive signal of controlling or change is exported by this main driver 103; And produce a control signal S2, in order to the drive signal of controlling or change is exported by this less important driver 105.This phase shift block 107 can pass through to regulate the phase shift angle between control signal, and then changes DC current gain.The definition of phase shift angle is and starts this synchronous rectifier 201 and 203 (being driven by less important driver 105), and the phase difference that starts its corresponding main switch element 201a-b and 203a-b (being driven by main driver 103).Through regulating this phase difference, the DC current gain of this resonant mode transducer can reduce effectively and/or along with the frequency monotonicity keep.

Fig. 3 discloses the LLC serial-resonant converter circuit sketch map of example embodiment of the present invention, and it is controlled direct current through switching frequency and increases the electricity gain.Though the resonant mode transducer can be reached by various execution mode, its operation is all identical in essence and summation is following.The square pulse wave of one voltage VAB is according to the voltage Vin that is provided and driving switch element 201a-b or 203a-b produce.This rectangular wave voltage VAB then is applied in a resonant circuit, is one in the present embodiment and has the LLC resonant circuit (resonant tank circuit) that inductance is connected with capacitances in series.Energy then is passed to a transformer T 211 first siding rings and produces voltage VL 219 in the above through this resonant circuit, and its transformer turn ratio 229 is n: 1.

For instance, these resonant mode transducer 101 circuit leftmost sides have a rectangular wave voltage generator 225a in dotted line 225 left elements.This rectangular wave generator 225a comprises main switch element 201a-b and 203a-b, in order to produce a rectangular wave input voltage VAB 217 to this LLC resonant network 235.These resonant mode transducer 101 circuit rightmost sides comprise a rectifier network 227a in dotted line 227 right-hand elements (transformer load).This rectifier network 227a produces direct current voltage output Vo through rectification in the AC current of transformer T 211 second siding ring gained.In addition, this rectifier network 227a also comprises synchronous rectifier 201 and 203.Actually practice full-bridge type capable of using and/or the all-wave resonant circuit is accomplished, also can use other to practice certainly.

For instance, when switch element 201a-b conducting, less important driver 105 starts synchronous rectifier 201, and transformer T211 second siding ring first half 215a passes through synchronous rectifier 201 to the load transfer energy.Likewise, during the negative sense input half period, the Lower Half 215b conducting of this second siding ring, to send the negative sense half period to this load, the action that therefore needs this synchronous rectifier 203 is to allow electric current flow through this coil and corresponding switch element 203a-b.

In one embodiment, this rectifier network 227a also comprises an output capacitor (smoothingcapacitor) Co and load resistance RL.

The resonant circuit of this resonant network 235 is to comprising three assemblies of LLC circuit and naming, a resonant capacitance Cr 209 who promptly is connected in series with a resonant inductance Lr 205 and the magnetizing inductance Lm 207 of transformer T211.This resonant circuit then is connected to the first siding ring 213 of transformer T211 again, and the second siding ring 215a of this transformer T211 and 215b then are connected to this

synchronous rectifier

201 and 203 simultaneously.

In this embodiment; This resonant mode transducer 101; Comprise a rectangular wave generator 225a and the main switch element 201a-b that matches thereof and 203a-b, a resonant network 235 and various inductance thereof and an electric capacity and a rectifier network 227a, can be applicable to the power source conversion of ac/dc or DC-DC etc.Yet resonant mode transducer 101 also can be used for AC/DC conversion, DC/DC conversion or high frequency electric source conversion.Moreover; This resonant mode transducer 101 also can practice according to other known change-over circuit assembly and frameworks, comprises but is not restricted to series resonance, parallel resonance and/or series parallel resonance; LCC frameworks and so on etc., it incites somebody to action visible this phase shift block 107 applicable to any circuit structure.

In one embodiment, this phase shift block more comprise a feedback circuit, a voltage controlled oscillator (voltage-controlled oscillator, VCO), and a phase-shift controller.

Fig. 4 discloses the time-histories sketch map of the main driver of resonant mode transducer in the example embodiment of the present invention and the phase shifting angle of less important driver (phase shift differential).For instance, time-histories sketch map 300 is the time-histories sketch map of the LLC resonant mode transducer of Fig. 3.The voltage VAB that is supplied to resonant mode transducer 101 resonant networks 235 is rectangular wave input 301, and its voltage is by on the occasion of to the negative value alternate.As previously mentioned, be used for driving switch element 201a-b and 203a-b through main driver pulse 305 and 307, less important driver pulse 303 then provides drive signal to synchronous rectifier 203 (drive signal of synchronous rectifier 201 is not disclosed in Fig. 4).In typical operation, less important (synchronous rectifier) driver pulse 303 and corresponding main driver pulse 305 do not have phase retardation.Synchronous rectifier 201 and 203 open-minded simultaneously with corresponding main switch.

For instance, this main driver pulse 305 and corresponding synchronous rectifier driver pulse 303 be in much at one time point such as t2, and t5 etc. are by open-minded, continue a period of time after then in time point such as t3, t6 is closed; At t2, t5 constantly, VAB 301 rises to its peak value and at t3, t6 VAB constantly begins to descend.Therefore, this relation discloses Fig. 3 synchronous rectifier Q6203 and corresponding main switch element 203a and 203b (Q1 and Q4) and is activated in much at one time point, and has the delay phenomenon generation.Likewise, synchronous rectifier Q5201 and corresponding switch element 201a and 201b (Q2 and Q3) are unlocked in time point much at one, and it is corresponding to the pulse 307 of time point t0 and t4 generation.And close and between 305 beginnings of the main driving pulse of switch element 203a and 203b (Q1 and Q4), its corresponding phase place (angle) or time-histories can be expressed as-0 ° of α 1=(phase angle of time point t1) (Q1 of time point t2 (Q4) starts phase angle) in the pulse 307 of switch element 201a and 201b (Q2 and Q3).Because during this period of time, be the Dead Time between complementary switch Q1 (Q4) and Q3 (Q2) on the brachium pontis, so α 1 is called as the Dead Time phase angle.And Q1 (Q4) is a complementary switch with Q3 (Q2), then angle [alpha] 2=-180 °=(phase angle of time point t0)-(phase angle of time point t2), and α 3=180 °=(phase angle of time point t4)-(phase angle of time point t2).

When the signal of less important driver 105 was early early opened with respect to the signal of main driver 103, a new phase shifting angle α was imported into.For instance; This new phase shifting angle α can be expressed as: be engraved in the difference on phase place or the time-histories during the opening of the corresponding main driving pulse 305 of the less important driving pulse 303 of this synchronous rectifier 203 and corresponding switch element 203a-203b; Wherein this less important driving pulse 303 is signable for pulse 303a in Fig. 4, and it is opened but not open-minded in time point t2 in early time point t '.Its relational expression is-0 ° of α=(phase angle of time point t ') (phase angle of time point t2).Because this LLC resonant mode transducer 101 is one full-bridge type/all-wave series resonant converter, this DC current gain (nVo/Vin) is determined by switching frequency usually.Regulate but this phase shift angle also can be used for DC current gain, and this phase shift degree surpasses or all can further influence this gain less than this dead band time phase angle degree α 1.The scope of this phase shift α (angle) can be by-180 degree (comprising) to 180 degree (comprising), and in one embodiment, this range can be by-180 degree to 0 degree (comprising).For instance, this range can be by Dead Time phase angle to 0 degree, and more particularly, this range is by Dead Time phase angle to diode current flow phase angle.Aforesaid specified scope all comprises endpoint value.Moreover in other embodiments, this endpoint value can be approximation, but comprises in essence, only otherwise influence the identity property of its operation.

Fig. 5 A discloses the DC current gain curve that example embodiment of the present invention is simulated with the means of compensate for parasitic capacitance.For instance, required monotonicity DC current gain characteristic is disclosed in the curve 411 among the figure.Under this situation, the DC current gain of light load operation is reduced to null value step by step along with the increase of frequency of operation.And this is unlike the DC current gain curve 1009 (seeing also Fig. 1 C) of tool charge pump, and being prone to has the different operation frequency relatively with value.It should be noted that result that DC current gain curve 1009 is responded is because the electric capacity (like parasitic capacitance) that importing one adds makes output loading voltage Vo be promoted to due to the given voltage levvl from null value slowly smooth-going (like linear forms).Therefore, be necessary in order to the means that solve or improve charge pump effect in this resonant mode transducer.

For reaching aforesaid effect, such as among Fig. 2 announcement relatively a phase shift block 107 of these resonant mode transducer 101 assembly this DC current gain is fallen subtract when the HF switch of this resonant mode transducer is used.Enforcement and application about this phase shift block 107 will further be disclosed in the circuit diagram 500 among Fig. 6 A.Yet in order to clearly demonstrate, Fig. 5 B and Fig. 5 C also disclose the phase shift of resonant mode transducer in the various embodiments of the present invention and the graph of a relation between voltage gain.In Fig. 5 B, standardization DC current gain curve 413 is in changing along with x axle 415 different phase shift phase angle values.The enlarged drawing of gain curve 413 then is disclosed in Fig. 5 C in the block 417, and it is presented in the limited field of phase angle excursion between-30 degree to+30 degree.The value of this gain curve 413 continues to maintain null value, is the Dead Time phase angle until the phase angle value to the position that A is ordered, the Dead Time of the main driver of complementary switch in its also corresponding switch bridge (switch bridge).Increase above after the A point in phase place, DC current gain just surpasses null value and is the monotonicity increase.Therefore, DC current gain can fall and reduce to null value, if the B point (phase shifting angle is 0 degree) of phase angle in figure is when moving to the A point.

Resonant mode transducer combo one phase shift block is to regulate the circuit diagram of DC current gain in Fig. 6 A announcement example embodiment of the present invention.For instance, the output voltage V o of phase shift block 503 these resonant mode transducers 501 of reception of this application circuit 500 is as input.The voltage Vo of input is sent to an error amplifier EA 505 of this phase shift block, and compares with reference voltage (like the voltage of corresponding required voltage gain) more subsequently.Produce error voltage signal Vea behind two signals that this error amplifier 505 receives.

This error voltage signal Vea is sent to a resonant mode transducer control module 511 as input.This resonant mode transducer control module 511 (like the control chip MC33067 of ONsemi) can be efficient ZVT (ZVS) controller; Use as off-line, ac/dc or DC/DC conversion, its utilize the frequency adjustment fixedly the shut-in time or fixedly Dead Time come control circuit.The error voltage signal Vea that uses can be used as the input of the frequency adjustment control input end 511a of this resonant mode transducer control module 511, in order to the adjustment switching frequency.509 of resistance R _ f can be in order to blanketing frequency response accordingly.Error voltage signal Vea also is sent to a Dead Time control input end 511b of resonant mode transducer control module 511, in order to the Dead Time of switch element in the regulating circuit.Vea inputs to 511b through resistance R d 507 and switch element 513.Resistance R o 515 and electric capacity 517 are used for filtering.The adjusting of frequency adjustment and Dead Time is inter-related like this.Therefore the adjusting of frequency adjustment and phase shifting angle also is mutually related.

Like this, an output signal 519 is by 511 generations of this resonant mode transducer control module, and this signal will be applicable to the less important drive signal S2 that generates resonant mode transducer 501.S2 can produce the time of delay (how represent second (nanoseconds)) of a specified rate again between this less important drive signal S2 and this main drive signal S1 through a delay circuit 521 (shown in figure, can be resistor-capacitor circuit-diode (RCD) institute formations).This delay more may be interpreted as phase delay alpha.As shown in the figure, signal S1 and S2 are passed to the main driver 103 and switch element and the synchronous rectifier of less important driver 105 to drive this resonant mode transducer 501 respectively of resonant mode transducer more respectively.

Fig. 6 B and Fig. 6 C disclose in the various embodiments of the present invention application sketch map with the separate phase shift block of FREQUENCY CONTROL and phase shifting control.For instance, Fig. 6 B discloses a phase-shift controller 527, and it provides main switch element Q1 and Q4 and switch element Q2 and the Q3 that outputs signal to this resonant mode transducer 101.Again, a frequency controller 523 provides the output signal to regulate the frequency of this resonant mode transducer 101.This phase-shift controller and this frequency controller are mutually independently.Independent frequency controller 523 and phase-shift controller 527 mutual connection through a signal generator 525.In this assembly, this signal generator 525 is received from the signal of frequency controller 523 outputs and synchronous rectifier Q6 and the Q5 of drive signal to this resonant mode transducer 101 is provided.Therefore this signal generator 525 produces the main and less important driver that signal S1 and S2 control this resonant mode transducer 101 according to this respectively.Offer frequency controller 523 and phase-shift controller 527 in the feedback output voltage V o of the rectifier network 227a of this resonant mode transducer 101, and each controller is operated its function separately based on its input again.

It is mutual when independent that Fig. 6 C discloses example embodiment medium frequency control of the present invention and phase shifting control, frequency and phase shift accordingly result graph of a relation.For instance, frequency curve 529 and phase shift curve 531 change according to the voltage feedback signal of x axle 533 expressions separately.Along with feedback voltage signal increases, this frequency curve 529 falls progressively between

voltage range

535a and 535b, and reduces to low frequency (like 100K) by high frequency (like 400K).Simultaneously, phase shift curve 531 begins to rise progressively, but between

identical voltage range

535a and 535b, then all keeps fixing with scope thereafter.Independent control that it should be noted that frequency and phase shift and Fig. 6 A are that frequency and phase shift are mutually related and control the identical control result of generation.

The application assembly that other of circuit 500 are different comprises to utilize and adds error amplifier and remove to regulate output voltage, also is contained in the scope of this example embodiment.For instance, the resonant mode transducer uses different error amplifiers to regulate the circuit diagram of the phase shift block institute assembly of DC current gain in Fig. 6 D announcement example embodiment of the present invention.Method shown in this assembly corresponding diagram 6B and Fig. 6 C, wherein FREQUENCY CONTROL and phase shifting control obtain identical DC current gain regulating effect by the execution of Different control device in circuit.In the present embodiment, circuit 538 and circuit 500 be the same is furnished with a phase shift block 537, and itself and 501 assembly of resonant mode transducer are to receive a feedback signal Vo.Output voltage signal (Vo) inputs to operation (work) frequency of an error amplifier EAF 539 of this phase shift block 537 with this circuit 535 of joint accent with a given reference voltage Vref in regular turn.The output Fea of this error amplifier EAF 539 inputs to this resonant mode transducer control module 511 through a resistance R _ f.Be that with circuit 500 differences this output signal Fea also provides to amplifier circuit EAD 541, it is a frequency feedback amplifier, in order to the control lag time.The output signal Dea of amplifier EAD is coupled to a switch Qd again, the signal S1 of phase shift and the phase shifting angle between S2 and the conditioning signal is arranged between providing mutually according to this.It should be noted that this circuit 538, when frequency adjustment was lower than some values such as 400K, output signal Fea was greater than reference value Fref, thereby it is saturated to make amplifier EAD 541 be negative sense.Like this, time of delay between signal S1 and the S2 and the phase shifting angle due to it then reduce to minimum value.

And as the output signal Fea of amplifier EAF 539 during less than reference value Fref, thereby this amplifier EAD541 output signal Dea will be according to conducting degree control lag extent time phase of the difference control switch Qd between Fea and the Fref.

Fig. 6 E discloses the flow chart of regulating resonant mode transducer DC current gain in the example embodiment of the present invention.In order to the flow process 540 of activation gain-adjusted, frequency adjustment and Dead Time control, for instance, circuit 500 that can Fig. 6 A or the circuit 538 of Fig. 6 D are carried out.In the step 543 of this flow process 540, phase shift block 503 produces the main driver of one first control signal S1 with control resonant mode transducer 501.In step 545,503 of this phase shift block produce the less important driver of one second control signal S2 with control resonant mode transducer 501.And this phase shift block 503; In step 547; Then one of collaborative this resonant mode transducer 501 feedback assembly (shown in circuit 500 and 538) operation, the phase shifting angle that at least partly is based on first control signal and second control signal is to control a DC current gain of this resonant mode transducer.This phase shifting angle or differ in order to compensating gain condition and/or other and can influence the various characteristic of required yield value.

The resonant mode transducer is in time according to the behavior timing diagram of phase shifting angle between main and less important driver in Fig. 7 A to Fig. 7 E announcement various embodiments of the present invention, and wherein this phase shifting angle is less than the Dead Time phase angle.For instance, the upper section of each accompanying drawing show electric current preset time district separated interior in the trend of resonant mode converter circuit; The below part of each accompanying drawing then be presented at preset time the district at a distance from, the phase shifting angle that between the main and less important driver of resonant mode transducer, is taken place particularly demonstrates the oscillogram of each electric current in the circuit.

The explanation of Fig. 7 A is following:

Between time point t0 to t1:

Synchronous rectifier Q6 by circuit 600 in less important driver start to ON state 603, shown in graph of a relation 602, synchronous rectifier Q6 promptly is forced the conducting electric current, in figure shown in the circuit 600.

2. because electric current I Lr flow to switch element Q3 from switch element Q2 through resonant circuit, and the electric current I Q6 of synchronous rectifier Q6 then flow to source electrode by drain electrode, cause capacitor C o to produce discharging current ICo, as illustrate shown in 602.

The explanation of Fig. 7 B is following:

Between time point t1 to t2:

1. after switch element Q2 and Q3 are closed to OFF state 607, as illustrate shown in 606, the electric current I Lr that the flows through resonant inductance body diode of switch element Q1 and Q4 of flowing through, as illustrate waveform shown in 606 609, at this moment between some electric current I Lr begin to rise.

2. because the electric current I Lr of resonant inductance that flows through is identical with direction between time-histories t0～t1, electric current I Q6 still flow to source terminal by drain electrode end, and makes capacitor C o discharge, as illustrates shown in 606.

The explanation of Fig. 7 C is following:

Between time point t2 to t2 ':

1. as shown in the diagram 612, switch element Q1 and Q4 are in a conducting state 613 at present, the electric current I Lr of the resonant inductance of flowing through flow through switch element Q1 and Q4, as illustrate shown in 612.

2. electric current I Lr does not change direction in the section at this moment, and the electric current I Q6 of the synchronous rectifier Q6 that therefore flows through still flows to source electrode from drain electrode, and makes this capacitor C o discharge, as illustrates shown in 612.

The explanation of Fig. 7 D is following:

At time point t2 ' between t3:

1. behind time point t2 ', the electric current I Lr of this resonant inductance of flowing through changes its direction, as illustrates shown in 616.

2. electric current I Q6 is existing flow to drain electrode from source electrode, and makes this capacitor C o charging, as illustrates shown in 616.

3. behind time point t3, synchronous rectifier Q5 then transfers unlatching ON state 617 to shown in diagram 616, and its operational process is identical with synchronous rectifier Q6.

Fig. 7 E sums up Fig. 7 A to Fig. 7 D and explains as follows:

During time point t0～t3:

1. the current value sum total ICo+IRL of electric capacity and load resistance of flowing through equal to flow through the respectively current value summation of electric current I Q5 and IQ6 of synchronous rectifier Q5 and Q6.

2. the current waveform that produces by current value summation ICo+IRL, as illustrate shown in 620, it is charging current that the waveform table above the x axle is shown in this time point; And x axle below person is a discharging current.

3. shown in diagram 620, average discharge current is greater than charging current.Therefore, can reach a compensating effect makes load voltage Vo be discharged to required magnitude of voltage.This method of regulating the gain of resonant mode transducer voltage is reached according to the adjusting of phase delay, Dead Time and/or switching frequency by a phase shift block 107.

Fig. 8 A to Fig. 8 E discloses resonant mode transducer in the various embodiments of the present invention in time according to the behavior timing diagram of phase shifting angle between main and less important driver, wherein should be main and less important driver between phase shifting angle greater than a Dead Time phase angle, and less than 0 degree.Below to be same as the process description discussion of Fig. 7 A-Fig. 7 E.

The explanation of Fig. 8 A is following:

Between time point t0 to t1:

1. be activated to ON state 703 at synchronous rectifier Q6, shown in graph of a relation 702, synchronous rectifier Q6 promptly is forced conducting electric current I Q6, as illustrates shown in 700.

2. flow to the body diode of switch element Q1 owing to electric current I Lr from the body diode of switch element Q4, as illustrate shown in 700, the electric current I Q6 of synchronous rectifier Q6 flow to source electrode by drain electrode, causes capacitor C o to produce discharging current ICo, as illustrates shown in 702.

The explanation of Fig. 8 B is following:

Between time point t1 to t1 ':

1. be opened into the ON state at switch element Q1 and Q4, cause the electric current I Lr of the resonant inductance of flowing through flow through switch element Q1 and Q4, as illustrate shown in 706.

2. because the flow through electric current I Lr of resonant inductance of section does not change direction at this moment, so the electric current I Q6 of synchronous rectifier Q6 still flow to source terminal by drain electrode end, and make capacitor C o produce discharging current ICo, as illustrate shown in 706.

The explanation of Fig. 8 C is following:

At time point t1 ' between t2:

1. the electric current I Lr of resonant inductor of flowing through changes its direction in time point t1 ' back, as illustrates shown in 710.

2. the electric current I Q6 of synchronous rectifier Q6 of flowing through will flow to drain electrode from source electrode, and make this capacitor C o charging, the waveform 711 shown in diagram.

The explanation of Fig. 8 D is following:

Between time point t2 to t3:

1. as shown in the diagram 714, after switch element Q1 and Q4 are closed to OFF state 715, the flow through body diode of switch element Q2 and Q3 of the electric current I Lr of this resonant inductance of flowing through.

Since the electric current I Lr of the inductance of flowing through as having identical direction to electric current I Lr between t2 with time-histories t1 ', the electric current I Q6 of the synchronous rectifier Q6 that therefore flows through still from source and course to the utmost point and makes this capacitor C o charging, as illustrates announcement person in 714.

3. behind time point t3, synchronous rectifier Q5 transfers unlatching ON state 717 to, and its operational process is identical with synchronous rectifier Q6.

Fig. 8 E sums up Fig. 8 A to Fig. 8 D and explains as follows:

During time point t0～t3:

1. the current value sum total ICo+IRL of electric capacity and load resistance of flowing through equal to flow through the respectively current value sum of electric current I Q5 and IQ6 of synchronous rectifier Q5 and Q6.

2. the current waveform that produces by current value summation ICo+IRL, as illustrate shown in 720, it is charging current that the waveform table above the x axle is shown in this time point; And x axle below person is a discharging current.

3. shown in diagram 720, average charge flows greater than discharging current.Therefore, can reach a compensating effect makes load voltage Vo charge to the proper level value.This method of regulating the gain of resonant mode transducer voltage is reached according to the adjusting of phase delay, Dead Time and/or switching frequency by a phase shift block 107.

Fig. 9 discloses the phase shift of a resonant mode transducer in the example embodiment of the present invention and regulates strain stress relation figure, influences DC current gain thereby regulate the phase shift angle through the adjusting Dead Time.Wherein the delay circuit 521 of this phase shift block 503 receives signal S2 and generation and the dephased input signal S1 of S2 to influence voltage gain.For instance, the delay between the S1S2 that is imported by delay circuit 521 be a fixed value as can be 150ns, this value does not change with circuit work frequency, promptly shown in the horizontal linear in the chart 800 801.In timing diagram 810 and 820, disclose respectively RCD postpone under high frequency (like height to 500K) and low frequency situation (like 100K) all identical.Be, the Dead Time characteristic of this resonant mode converter circuit tapers off in the scope of frequency increments differently, promptly shown in the straight line in the chart 800 803.Timing diagram 810 explained, in frequency applications, this dead band time 807 less than RCD time of delay 801 (like 50ns＜150ns).Timing diagram 820 explained, in low frequency applications, this dead band time 811 greater than RCD time of delay 801 (like 500ns＞150ns).

Change in frequency of operation; Fix time of delay; The switch element Q1 (Q4) of resonant circuit and the Dead Time between Q2 (Q3) are then according under the situation of regulating shown in the chart 800, and the main switch and the synchronous rectifier Q5 of correspondence and the phase shift angle between Q6 also are conditioned.Under same frequency is responded, when Dead Time becomes to being similar to time of delay, be equivalent to crosspoint C again.An advantage of the present invention is that through the assembling structure of Fig. 6 A or Fig. 6 D, the frequency of resonant mode transducer 101 and phase shift angle can be regulated and control simultaneously.

Demonstration system that the present invention discussed and technology can provide the short-cut method of the key property of regulating a resonant mode converter circuit, especially on design is used, more utilize synchronous rectifier to come the start switch.Through this resonant circuit 101 of assembly and a phase shift block 107, this resonant mode transducer is its voltage gain characteristic of scalable then.

Moreover this system can handle when light load operation and use charge pump effect or its inner effect that produces that produces according to parasitic capacitance.So example embodiment of the present invention can be carried out phase shifting control and in the change frequency scope, obtained lower voltage gain and meet design and consider.The technological means that disclose the front can be in order to lowering the voltage or the current stress of each element in circuit, and promote the stability and the reliability of circuit.

Aforesaid advantage all can be overlapped the assembly that is used for the resonant mode transducer, comprises like LLC, LCC, parallel connection, series connection, series parallel resonance and combination thereof, but is not limited to this.Moreover, at this description control resonant mode transducer DC current gain to increase the flow process of power supply service efficiency in the circuit, more can be further through software, hardware, firmware or combine software and/or firmware and/or hardware to implement.For example, Digital Signal Processing control can be in order to carry out the adjusting of frequency and phase place, and this driver and/or controller can be through relatively triangular signal and reference value signal produce frequency signal and/or phase shifting angle signal in the phase shift block 107/503 whereby.Through the method, frequency can be regulated through the triangular wave count value, and time of delay is then through changing digital signal processor relatively (digital signal processor, DSP) chip internal reference value and changing.But and in this described program also application specific integrated circuit (Application SpecificIntegrated Circuit, ASIC) and field programmable gate array (Field Programmable Gate Array FPGA) waits and to reach.

Technology of the present invention has practicality, novelty and progressive, files an application in accordance with the law.Can appoint by those skilled in the art even if the present invention has been described in detail by the above embodiments and to execute that the craftsman thinks and be to modify as all, yet not take off as attaching the scope of claim institute desire protection.

Claims

1. adjusting gain method that is applied to the resonant mode transducer, it comprises step:

Produce one first control signal, in order to control a main driver of a resonant mode transducer; And

Produce one second control signal, in order to control a less important driver of this resonant mode transducer, wherein this first control signal and this second control signal have a phase shifting angle, in order to control a DC current gain of this resonant mode transducer.

2. adjusting gain method as claimed in claim 1, wherein the scope of this phase shifting angle is to spending smaller or equal to+180 more than or equal to-180 degree.

3. adjusting gain method as claimed in claim 1, wherein the scope of this phase shifting angle is to spending smaller or equal to 0 more than or equal to-180 degree.

4. adjusting gain method as claimed in claim 1, a plurality of main switch elements of this main driver drives wherein, and this method more comprises step:

Given this main switch element one Dead Time.

5. adjusting gain method as claimed in claim 4, wherein the scope of this phase shift is to spending smaller or equal to 0 more than or equal to the Dead Time phase angle.

6. adjusting gain method as claimed in claim 4, wherein the scope of this phase shift is extremely smaller or equal to the diode current flow phase angle more than or equal to the Dead Time phase angle.

7. adjusting gain method as claimed in claim 4 more comprises step:

An output signal that receives this resonant mode transducer is as feedback, to produce this first control signal and this second control signal.

8. adjusting gain apparatus that is applied to the resonant mode transducer, it comprises:

One delay circuit; And

One control module is coupled to this delay circuit, and provides and export this delay circuit to, produces one first control signal to control a main driver of this resonant mode transducer in order to the output voltage according to a resonant mode transducer; And produce one second control signal to control a less important driver of this resonant mode transducer;

Wherein this first control signal and this second control signal have a phase shifting angle, in order to control a DC current gain of this resonant mode transducer.

9. adjusting gain apparatus as claimed in claim 8, wherein the scope of this phase shifting angle is to spending smaller or equal to 0 more than or equal to-180 degree.

10. adjusting gain apparatus as claimed in claim 8, wherein the scope of this phase shifting angle is to spending smaller or equal to 0 more than or equal to a Dead Time phase angle.

11. adjusting gain apparatus as claimed in claim 8, wherein the scope of this phase shifting angle is for extremely spend smaller or equal to a diode current flow more than or equal to a Dead Time phase angle mutually.

12. adjusting gain apparatus as claimed in claim 8 more comprises:

One error amplifying circuit receives this output voltage of this resonant mode transducer, and produce an error voltage signal as the input of this control module to control a frequency of this resonant mode transducer.

13. adjusting gain apparatus as claimed in claim 12, wherein:

This error voltage signal is more in order to control a Dead Time of this resonant mode transducer.

14. adjusting gain apparatus as claimed in claim 12 more comprises:

One frequency feedback amplifying circuit is connected with this error amplifying circuit and this delay circuit, receives this error voltage signal to produce an output signal in order to control this phase shifting angle.

15. one regulates gain apparatus, it comprises:

One resonant mode transducer has a main driver and a less important driver; And

One phase shift block is coupled to this main driver and this less important driver, and this phase shift block produces one first control signal to control this main driver and to produce one second control signal with this less important driver of control;

Wherein this first control signal and this second control signal have a phase shift, in order to control a DC current gain of this resonant mode transducer.

16. adjusting gain apparatus as claimed in claim 15, wherein the scope of this phase shifting angle is to spending smaller or equal to 0 more than or equal to-180 degree.

17. adjusting gain apparatus as claimed in claim 15, wherein the scope of this phase shifting angle is to spending smaller or equal to 0 more than or equal to a Dead Time phase angle.

18. adjusting gain apparatus as claimed in claim 15, wherein the scope of this phase shift is for extremely spend smaller or equal to a diode current flow more than or equal to a Dead Time phase angle mutually.

19. adjusting gain apparatus as claimed in claim 15, wherein this phase shift block more receives one of this resonant mode transducer and exports signal as feedback, to produce this first control signal and this second control signal.

20. adjusting gain apparatus as claimed in claim 19, wherein this phase shift block comprises:

One error amplifying circuit receives this output voltage of this resonant mode transducer, and produces an error voltage signal; And

One resonant mode transducer control module is coupled to this error amplifier, and receives this error voltage signal, in order to export this first control signal and second control signal.