DE102005026659B3 - Apparatus for compensating for interference on receiving a data signal on which an interference signal is superimposed esp. a sinusoidal interference signal - Google Patents

Abstract

The apparatus includes a transformer (1) which transforms the received signal from a time domain to a frequency domain to provide several complex amplitudes at different carrier frequencies, and provides a complex first interference amplitude at a different carrier frequency. A calculator (41-43) generates second and third complex signal amplitudes at unused second and third carrier frequencies. A subtractor (3) subtracts the second and third amplitudes from the complex amplitude of the data signal at the second carrier frequency. Independent claims also cover a compensation method.

Description

The The invention relates to an apparatus and a method for compensation of disorders upon receiving a superposed with a noise signal useful signal.

The Technical field of the invention relates to the transmission of voice data and associated Fees designation signals or Teletax signals and the simultaneous transmission of data in one higher Frequency band over a common subscriber line.

disorders, in particular in the data band are generated by the charge determination signals high signal level (for example the TTX (teletax) signal) at a frequency of 12 or 16 kHz up to 5 Vrms on the subscriber line is) and their higher harmonic harmonics caused by non-linear properties of the amplifier the subscriber line circuit (SLIC = Subscriber Line Interface Card) of the transmitter are caused. These harmonic harmonics or briefly disrupt harmonics Transmit signals (upstream signals) the ADSL data transmission (Asymmetric Digital Subscriber Line) on the subscriber line.

Usually is for asymmetric data transmission over ordinary Telephone lines a multi-tone method (DMT = Discrete Multitone; Discrete multitone modulation). A significant advantage of ADSL transmission techniques across from ordinary transmission techniques is that conventional Cable networks for a transmission can be used usually with each other copper double cores be used. Under the transfer procedure with a high data rate based on digital subscriber lines (DSL = Digital Subscriber Line) are several VDSL (Very High Date Rate DSL = high-speed DSL) arrangements known, for which purpose e.g. method such as CAP (Carrierless Amplitude Phase), DWMT (Discrete Wavelet Multitone), SLC (Single Line Code) and DMT (Discrete Multitone) can be used.

The US 6,570,514 B1 discloses a compensator for compensating for linearity errors, such as harmonic distortion and intermodulation interference, and which describes an apparatus including phase shifting means and exponentiation means for generating a compensation signal such that the linearity error jamming signals at the system output cancel out while maintaining the desired fundamental signal.

The US 6,157,680 A describes a suppression method for audio interference and a corresponding device. For this purpose, different steps of supplying a transmit signal to a modulator, feeding the output of the modulator to a non-linear device, feeding the output of the non-linear device to an echo canceller, supplying a receive signal that is a disturbance including, to a first filter to obtain an error signal, updating the echo canceller using the error signal, the echo canceller providing an echo replica signal, filtering the echo replica signal in a second filter, to obtain a filtered echo replica signal, and subtracting the filtered echo replica signal from the output of the modulator to obtain an error-corrected signal. With this method, however, different carrier signals of a multiple audio signal can not be compensated by means of specific predetermined compensation signals.

Another method for distortion compensation is in US 5,872,814 A described.

The patent application DE 103 50 340.4-31 with the title "Apparatus and Method for Transmission of an Analog Data Stream with Compensation of Spectral Side Shares" by the applicant of the present patent application shows a solution to the problem discussed above. In particular, a compensation device is described for compensating the spectral secondary components of a multi-tone signal transmitted on a carrier signal, which are superimposed on at least one further carrier signal. This compensates for the effects of harmonics in the data system. Disadvantageously, the so-called leakage effect (or even leak effect) is not taken into account in the above patent application. The leak effect is produced by any sound that is not directly on the frequency raster of the time-frequency transformation. This leads to crosstalk in other frequency ranges and thus to interference in the detection at other carrier frequencies. In addition, consuming and time-consuming experiments by the applicant have shown that the method of the above-cited patent application in a very klei NEN level at the carrier frequency of the charge determination signal only partially works.

The The object of the present invention is to provide a better, in particular more effective compensation of disturbances when receiving a with a sinusoidal Interference signal superimposed To provide useful signal. Another task is the disturbances better due to the harmonics of the sinusoidal useful signal compensate. Another object of the present invention is in it, even the glitches to compensate for the leak effect.

According to the invention, at least one of these objects by a device with the features of Patent claim 1 and / or by a method with the features of claim 10.

• (a) eine Transformationsvorrichtung, welche das empfangene Nutzsignal von einem Zeitbereich in einen Frequenzbereich zur Bereitstellung einer Vielzahl von komplexen Amplituden bei verschiedenen Trägerfrequenzen transformiert und eine durch die Grundwelle verursachte, komplexe erste Störamplitude bei einer von dem Nutzsignal ungenutzten ersten Trägerfrequenz bereitstellt;
• (b) eine Berechnungsvorrichtung, welche eine durch die Grundwelle verursachte, komplexe zweite Störamplitude bei einer zweiten Trägerfrequenz und/oder zumindest eine durch eine der Oberwellen verursachte, komplexe dritte Störamplitude bei der zweiten Trägerfrequenz aus der ersten Störamplitude erzeugt; und
• (c) eine Subtrahiervorrichtung, welche die zweite Störamplitude und/oder eine oder mehrere dritte Störamplituden von der komplexen Amplitude des transformierten Nutzsignals bei der zweiten Trägerfrequenz subtrahiert. (Patentanspruch 1)

Accordingly, it is provided:
An apparatus for compensating for disturbances caused by a fundamental wave and by at least one harmonic of an interfering signal, in particular a sinusoidal interfering signal, upon receiving a signal superimposed with the interfering signal, having the following features:

• (a) a transformation device that transforms the received payload signal from a time domain into a frequency domain to provide a plurality of complex amplitudes at different carrier frequencies and provides a complex first disturbance amplitude caused by the fundamental wave at a first carrier frequency unused by the payload signal;
• (b) a computing device that generates a complex second disturbance amplitude caused by the fundamental wave at a second carrier frequency and / or at least one complex third disturbance amplitude caused by one of the harmonics at the second carrier frequency from the first disturbance amplitude; and
• (c) a subtracting device which subtracts the second interference amplitude and / or one or more third interference amplitudes from the complex amplitude of the transformed useful signal at the second carrier frequency. (Claim 1)

• (a) Transformieren des empfangenen Nutzsignals von einem Zeitbereich in einen Frequenzbereich zur Bereitstellung einer Vielzahl von komplexen Amplituden bei verschiedenen Trägerfrequenzen;
• (b) Bereitstellen einer durch die Grundwelle verursachten, komplexen ersten Störamplitude bei einer ersten Trägerfrequenz, die nicht von dem Nutzsignal genutzt wird;
• (c) Berechnen einer durch die Grundwelle verursachten, komplexen zweiten Störamplitude bei einer zweiten Trägerfrequenz aus der ersten Störamplitude und/oder Berechnen zumindest einer durch eine der Oberwellen verursachten, komplexen dritten Störamplitude bei der zweiten Trägerfrequenz aus der ersten Störamplitude; und
• (d) Subtrahieren der zweiten Störamplitude und/oder einer oder mehrerer der dritten Störamplituden von der komplexen Amplitude des transformierten Nutzsignals bei der zweiten Trägerfrequenz. (Patentanspruch 10)

A method for compensating for disturbances which are caused by a fundamental wave and by at least one harmonic of an interference signal, in particular a sinusoidal interference signal, when receiving a useful signal superimposed with the interference signal, the method according to the invention comprising the following steps:

• (a) transforming the received payload signal from a time domain into a frequency domain to provide a plurality of complex amplitudes at different carrier frequencies;
• (b) providing a complex first disturbing amplitude caused by the fundamental wave at a first carrier frequency not used by the wanted signal;
• (c) calculating a complex second interference amplitude caused by the fundamental wave at a second carrier frequency from the first interference amplitude and / or calculating at least one complex third interference amplitude caused by one of the harmonics at the second carrier frequency from the first interference amplitude; and
• (d) subtracting the second interference amplitude and / or one or more of the third interference amplitudes from the complex amplitude of the transformed useful signal at the second carrier frequency. (Claim 10)

advantageously, is obtained by subtracting the second interference amplitude from the complex Amplitude of the transformed useful signal of the leak effect compensated. Furthermore is obtained by subtracting the third noise amplitude or the plurality of third noise amplitudes achieved that the disturbances, which are caused by the harmonics of the sinusoidal interference signal, be compensated. In particular, the useful signal is an ADSL data signal and the interfering signal is the fee determination signal.

advantageous Refinements and developments of the invention will become apparent the dependent claims as well as the description and the reference to the drawings.

According to one preferred embodiment of the invention is superimposed with the interference signal Payload signal by means of a discrete multitone modulation method modulated.

According to one Another preferred embodiment forms the fundamental wave of the sinusoidal interference signal a charge determination signal out.

According to one Another preferred embodiment leads the transformation device for transforming the received useful signal from the time domain in the frequency domain a Fourier transform, in particular a fast Fourier transform, by.

• – eine erste Berechnungseinheit, die eine komplexe vierte Störamplitude der Grundwelle des Störsignals aus der ersten Störamplitude bei der ersten Trägerfrequenz erzeugt;
• – eine Potenziervorrichtung, die durch Potenzbildung oder Phasendrehung eine komplexe fünfte Störamplitude bei der i-ten Oberwelle aus der erzeugten vierten Störamplitude der Grundwelle erzeugt;
• – eine erste Gewichtungsvorrichtung, die mittels einer Gewichtungsfunktion, die eine Nichtlinearität einer Verstärkungseinheit einer Sendeeinheit modelliert, die das Störsignal sendet, eine gewichtete, komplexe fünfte Störamplitude aus der fünften Störamplitude erzeugt;
• – eine dritte Berechnungseinheit, die die dritte Störamplitude bei der zweiten Trägerfrequenz aus der gewichteten fünften Störamplitude erzeugt; und
• – eine zweite Berechnungseinheit, die die zweite Störamplitude bei der zweiten Trägerfrequenz aus der vierten Störamplitude der Grundwelle erzeugt.

According to a preferred embodiment of the invention, the calculation device comprises:

• A first calculation unit which generates a complex fourth interference amplitude of the fundamental wave of the interference signal from the first interference amplitude at the first carrier frequency;
• A potentiometer which, by power generation or phase rotation, generates a complex fifth noise amplitude at the ith harmonic from the generated fourth noise amplitude of the fundamental wave;
• A first weighting device that generates a weighted complex fifth disturbance amplitude from the fifth disturbance amplitude by means of a weighting function that models a non-linearity of an amplification unit of a transmission unit that transmits the interference signal;
• A third calculation unit that generates the third interference amplitude at the second carrier frequency from the weighted fifth interference amplitude; and
• A second calculation unit which generates the second interference amplitude at the second carrier frequency from the fourth interference amplitude of the fundamental wave.

• – eine Potenziervorrichtung, die durch Potenzbildung oder Phasendrehung eine erste Störamplitude bei der i-ten Oberwelle aus der ersten Störamplitude erzeugt;
• – eine fünfte Berechnungseinheit, die die dritte Störamplitude bei der zweiten Trägerfrequenz aus der erzeugten ersten Störamplitude bei der i-ten Oberwelle erzeugt; und
• – eine vierte Berechnungseinheit, die die zweite Störamplitude bei der zweiten Trägerfrequenz aus der ersten Störamplitude bei der ersten Trägerfrequenz erzeugt.

According to a further preferred development, the calculation device has:

• A potentiometer which, by power generation or phase rotation, generates a first spurious amplitude at the ith harmonic from the first spurious amplitude;
• A fifth calculation unit which generates the third interference amplitude at the second carrier frequency from the generated first interference amplitude at the i-th harmonic wave; and
• A fourth calculation unit which generates the second interference amplitude at the second carrier frequency from the first interference amplitude at the first carrier frequency.

• – die Potenziervorrichtung, die durch Potenzbildung oder Phasendrehung eine erste Störamplitude bei der i-ten Oberwelle aus der ersten Störamplitude erzeugt;
• – eine zweite Gewichtungsvorrichtung, die mittels einer komplexen Gewichtungsmatrix eine gewichtete erste Störamplitude bei der i-ten Oberwelle aus der ersten Störamplitude bei der i-ten Oberwelle erzeugt;
• – eine dritte Berechnungseinheit, die die dritte Störamplitude bei der zweiten Trägerfrequenz aus der gewichteten ersten Störamplitude bei der i-ten Oberwelle erzeugt; und
• – die vierte Berechnungseinheit, die die zweite Störamplitude bei der zweiten Trägerfrequenz aus der ersten Störamplitude bei der ersten Trägerfrequenz erzeugt.

According to a further preferred development, the calculation device has:

• The exponentiation device which generates by power generation or phase rotation a first interference amplitude at the ith harmonic from the first interference amplitude;
• A second weighting device which generates by means of a complex weighting matrix a weighted first perturbation amplitude at the ith harmonic from the first perturbation amplitude at the ith harmonic;
• A third calculation unit that generates the third interference amplitude at the second carrier frequency from the weighted first interference amplitude at the ith harmonic; and
• The fourth calculation unit which generates the second interference amplitude at the second carrier frequency from the first interference amplitude at the first carrier frequency.

• – eine Realteilbildungsvorrichtung, welche eingangsseitig eine komplexe Störamplitude empfängt und ausgangsseitig einen Realteil der empfangenen Störamplitude bereitstellt;
• – eine Imaginärteilbildungsvorrichtung, welche eingangsseitig die komplexe Störamplitude empfängt und ausgangsseitig einen Imaginärteil der empfangenen Störamplitude bereitstellt,
• – eine Multipliziervorrichtung, welche einen Vektor aus dem Realteil und dem Imaginärteil der empfangenen Störamplitude mit einer Korrekturmatrix multipliziert, und die empfangene Störamplitude bei einer ersten Frequenz auf eine Störamplitude bei einer zweiten Frequenz korrigiert; und
• – eine Phasendrehungseinheit, welche eine Phasendrehung des mit der Korrekturmatrix multiplizierten Imaginärteils durchführt; und
• – eine Addiervorrichtung, die den von der Multipliziervorrichtung ausgangsseitig bereitgestellten Realteil und den von der Phasendrehungsvorrichtung bereitgestellten Imaginärteil addiert.

According to a further preferred development, the calculation unit has:

• A real-part-forming device which receives on the input side a complex interference amplitude and on the output side provides a real part of the received interference amplitude;
• An imaginary part-forming device, which receives on the input side the complex interference amplitude and on the output side provides an imaginary part of the received interference amplitude,
• - A multiplier which multiplies a vector of the real part and the imaginary part of the received noise amplitude with a correction matrix, and corrects the received noise amplitude at a first frequency to a noise amplitude at a second frequency; and
• A phase rotation unit which performs a phase rotation of the imaginary part multiplied by the correction matrix; and
• An adder which adds the real part provided by the multiplier on the output side and the imaginary part provided by the phase rotation device.

Preferably are the real part forming device and the imaginary part forming device provided in an extracting device.

• – eine erste Filtervorrichtung, die das empfangene Nutzsignal ausgangsseitig nur bei der Frequenz der Grundwelle durchlässt;
• – eine erste Transformationseinheit, die das mittels der ersten Filtervorrichtung gefilterte Nutzsignal vom Zeitbereich in den Frequenzbereich transformiert;
• – eine zweite Filtervorrichtung, die das empfangene Nutzsignal ausgangsseitig nur nicht bei der Frequenz der Grundwelle des Störsignals durchlässt;
• – und eine zweite Transformationseinheit, die das mittels der zweiten Filtervorrichtung gefilterte Nutzsignal vom Zeitbereich in den Frequenzbereich transformiert.

According to a further preferred development, the transformation device has:

• - A first filter device which transmits the received useful signal on the output side only at the frequency of the fundamental wave;
• A first transformation unit which transforms the useful signal filtered by the first filter device from the time domain into the frequency domain;
• A second filter device which does not transmit the received useful signal on the output side only at the frequency of the fundamental wave of the interference signal;
• - And a second transformation unit, which transforms the filtered by the second filter device useful signal from the time domain in the frequency domain.

The Invention will be described below with reference to the schematic figures the drawing specified embodiments explained in more detail. It demonstrate:

1 a schematic block diagram of a first embodiment of the device according to the invention;

2 a schematic block diagram of a second embodiment of the device according to the invention;

3 a schematic block diagram of a third embodiment of the device according to the invention;

4 a schematic block diagram of a preferred embodiment of the calculation unit according to the present invention;

5 a schematic block diagram of a fourth embodiment of the device according to the invention; and

6 a schematic flow diagram of a preferred embodiment of the method according to the invention.

In all figures are the same or functionally identical elements and signals - if nothing else is stated - with the same reference numerals have been provided.

1 shows a schematic block diagram of a first embodiment of the inventive device for compensation of interference caused by a fundamental wave ω0 and harmonics i · ω0 of a sinusoidal noise signal d [n], upon receiving a superposed with the noise signal d [n] useful signal s [ n] + d [n]. The device according to the invention has a transformation device 1 , a calculation device 21 and a subtracting device 3 on.

The transformation device 1 receives the useful signal s [n] + d [n] superimposed on the interference signal d [n] and transforms the received useful signal s [n] + d [n] from a time domain into a frequency domain and thus provides a multiplicity of complex amplitudes on the output side D _w [k], S _w [l] + D _w [l] at different carrier frequencies k, l ready. The indexing w stands for windowed (fenestrated). In particular, the transformation device 1 a complex first interference amplitude D _w [k] caused by the fundamental wave ω0 at a first carrier frequency k, the first carrier frequency k not being used by the useful signal s [n].

The calculation device 21 generates a complex second _{interference amplitude} A _ω0 [l] caused by the fundamental wave ω0 at a second carrier frequency l and / or a complex third _{interference amplitude} A _{i * ω0} [l] caused by the respective ith harmonic i × ω0 second carrier frequency l from the first interference amplitude D _w [k]. In particular, the second _{interference amplitude} A _ω0 [l] and the third _{interference amplitude} A _{i * ω0} [k] are derived from the first _{interference amplitude} D _w [k].

The subtracting device 3 subtracts the second _{interference amplitude} A _ω0 [l] and / or the respective third _interference amplitudes A _{i · ω0} [l] from the complex amplitude S _w [l] + D _w [l] of the transformed useful signal at the second carrier frequency l, so that the subtracting device 3 provides a noise-compensated useful signal S _w [l] in the frequency domain on the output side.

The calculation device 21 preferably has a first calculation unit 41 , a potentiator 5 , a first weighting device 61 , a third calculation unit 43 and a second calculation unit 42 on.

The right path of the calculation device 21 namely, the calculation unit 41 , the potentizer 5 , the first weighting device 61 and the third calculation unit 43 , Compensate the harmonic compensation of the interfering signal d [n]. The left path of the calculation device 21 namely, the first calculation unit 41 and the second calculation unit 42 , Compensates for the compensation of the leak effect.

The first calculation unit generates this 41 a complex fourth interference _amplitude A _{ω0 of} the fundamental wave ω0 of the interference signal d [n] from the first interference amplitude D _w [k] at the first carrier frequency k. The potentizer 5 then, by power generation or phase rotation in the complex, generates a complex fifth disturbance _amplitude A _{i · ω0} at the first carrier frequency k from the generated fourth disturbance _amplitude A _{ω0 of} the fundamental wave ω0.

In the following, the weighting device generates 61 a weighted, complex fifth _{interference amplitude} c _i * A _{i * ω 0} from the fifth _{interference amplitude} A _{i * ω 0} by means of a weighting function c _i . The weighting function c _i models the non-linearity of the amplification unit (SLIC) of the transmitting unit of the transmitter.

Finally, for the right path of the calculation device 21 generates the third calculation unit 43 the third _{interference amplitude} A _{i · ω0} [l] at the second carrier frequency l from the weighted fifth _{interference amplitude} c _i · A _{i · ω0} .

Finally for the left path of the calculation device 21 generates the calculation unit 42 the second _{interference amplitude} A _ω0 [l] at the second carrier frequency l from the fourth _{interference amplitude} A _{ω0 of} the fundamental wave ω0.

In particular, the useful signal s [n] + d [n] superimposed with the interference signal d [n] is modulated by means of a discrete multitone modulation method (DMT) and the fundamental wave ω0 of the sinusoidal interference signal D _w [k] forms a charge determination signal or teletax Signal whose fundamental or fundamental frequency is 12 or 16 kHz.

The transformation device 1 leads to the transformation of the received, superimposed with the interfering signal d [n] useful signal s [n] + d [n] in particular a Fourier transform, preferably a fast Fourier transform by.

In 2 a schematic block diagram of a second embodiment of the device according to the invention is shown. The second embodiment differs from the first embodiment according to 1 in the embodiment of the calculation device 21 , According to the second embodiment of the calculation device 21 are a potentizer 5 , a fifth calculation unit 45 and a fourth calculation unit 44 intended. The potentizer 5 generates by means of power generation or by means of a phase rotation a first _{interference amplitude} D _{i · ω0} at the ith harmonic from the first _{interference amplitude} D _w [k] at the first carrier frequency k. The following generates the fifth calculation unit 45 the third _{interference amplitude} A _{i · ω0} [l] at the second carrier frequency l from the generated first _{interference amplitude} D _{i · ω0} at the ith harmonic.

To complete the left hand path, which, as stated above, compensates for the leak effect, the fourth calculation unit generates 44 the second _{interference amplitude} A _{i · ω0} [l] at the second carrier frequency l from the first _{interference amplitude} D _w [k] at the first carrier frequency k.

Thus, the fourth calculation unit satisfies 44 according to 2 the functionality of the first and second calculation units 41 and 42 according to 1 , As in particular in 4 will show the calculation units 41 - 45 essentially correction matrices, so that by means of a matrix multiplication or multiple matrix multiplications, the functionalities of multiple calculation units - as shown above - can be merged into one calculation unit. This advantageously saves computation time and computing time.

The fifth calculation unit 45 approximately fulfills the functionality of the first and third calculation unit 41 and 43 and the first weighting device 61 according to 1 , wherein the functionality of the first calculation unit 41 is approximated by a scalar, complex multiplication.

3 shows a schematic block diagram of a third embodiment of the device according to the invention. The third embodiment according to 3 differs only in the embodiment of the calculation device 21 , According to the third embodiment of the computing device 21 are a potentizer 5 , a second weighting device 62 , a third calculation unit 43 and the fourth calculation unit 44 intended. The potentizer 5 generates by power generation or phase rotation a first _{interference amplitude} D _{i · ω0} at the ith harmonic from the first _{interference amplitude} D _w [k]. Thereupon, the second weighting device generates 62 by means of a complex weighting factor ĉ _i a weighted first _{interference amplitude} ĉ _i · D _{i · ω0} at the i-th harmonic from the first _{interference amplitude} D _{i · ω0} at the ith upper wave. In the following, the third calculation unit generates 43 to complete the right path of the computing device 21 the third _{interference amplitude} A _{i · ω0} [l] at the second carrier frequency l from the weighted first _{interference amplitude} ĉ _i · D _{i · ω0} at the ith harmonic.

To complete the left path (harmonic compensation), the fourth calculation unit generates 44 the second _{interference amplitude} A _ω0 [l] at the second carrier frequency l from the first _{interference amplitude} D _w [k] at the first carrier frequency k.

In 4 is a schematic block diagram of a preferred embodiment of the calculation unit 41 represented according to the present invention. 4 Although only shows one embodiment of the first calculation unit 41 , for the remaining calculation units 42 - 45 However, the same applies.

As already in 1 explained, generates the first calculation unit 41 the complex fourth interference _amplitude A _{ω0 of} the fundamental wave ω0 of the interference signal d [n] from the first interference amplitude D _w [k] at the first carrier frequency k. This functionality is preferably provided by means of the following units or devices. To clarify the functionality of the real part forming device 7 , the imaginary education unit 8th and the multiplier 9 is preceded by a mathematical consideration.

The sinusoidal interferer or the interference signal d [n] can be represented as follows:

lautet wie folgt:

The corresponding Fourier transformation of the interference signal d [n] after multiplication by a rectangular window

as follows:

wobei ω₁ und ω₂ gegeben sind als:

This results in the first interference amplitude D _w [k] at the first carrier frequency k:

where ω ₁ and ω _{2 are} given as:

If all complex numbers are divided into their real and imaginary parts, equation (4) can be written as matrix multiplication:

At this point, the correction matrix W (k, ω ₀ ) is introduced, which represents the relationship between the first perturbation amplitude D _w [k] and the complex amplitude A as matrix multiplication, which depends on the carrier frequency k and the fundamental wave ω0. The complex amplitude A consists of a real part Re (A) and an imaginary part Im (A). It should be added at this point that a multiplication of two random complex numbers x and y can be expressed by a matrix multiplication with special symmetric properties:

These symmetry properties are given in equation (8) only if the term A · ω ₂ in equation (4) can be neglected.

From the equations (4), (5) and (6), it is clearly understood that the DFT of the first disturbance amplitude D _w [k], k = 0, ..., N-1, can be generated when the complex amplitude A and the fundamental wave ω0 of the sinusoidal signal d [n] are known.

By means of an inversion, the complex amplitude or interference amplitude can then be specified if at least one value of the first interference amplitude D _w [k] and the fundamental wave or the frequency of the fundamental wave ω0 are known:

The real-part education device 7 Thus, it has the function of receiving the complex interference amplitude D _w [k] on the input side and of providing on the output side a real part Re (D _w [k]) of the first interference amplitude D _w [k].

Analogously, the imaginary dividing device receives 8th the first interference amplitude D _w [k] on the input side and on the output side provides an imaginary part Im (D _w [k]) of the received first interference amplitude D _w [k].

In the following, the multiplier multiplies 9 a vector from the real part Re (D _w [k]) and the imaginary part Im (D _w [k]) of the first disturbance amplitude D _w [k] with the correction matrix W ^-1 (k, ω0) representing the inverse to the correction matrix W (k, ω0), for correcting the received first interference amplitude D _w [k] at the first carrier frequency k to the fourth _{interference amplitude} A _{ω0 of} the fundamental wave ω0.

The phase rotation unit 10 performs a phase rotation of the imaginary part Im (D _w [k]) of the first disturbance amplitude D _w [k] multiplied by the correction matrix W ^-1 (k, ω0). The adding device 11 then adds that from the multiplier 9 on the output side provided real part and that of the phase rotation unit 10 provided imaginary part.

5 shows a schematic block diagram of a fourth embodiment of the device according to the invention. The fourth embodiment according to 5 differs essentially from the first embodiment according to 1 in the embodiment of the transformation device 1 , Furthermore, for the useful signal S _w [l], S _w [m], S _w [n] in the frequency range three carrier frequencies l, m, n, and thus also three identical calculation devices 21 ' - 23 ' for calculating the respective third _{interference amplitude} A _{i * ω 0} [1], A _{i * ω 0} [m], A _{i * ω 0} [n].

The transformation device 1 according to the fourth embodiment, a first filter device 12 , a first transformation unit 13 , a second filter device 14 and a second transformation unit 15 on.

The first filter device 12 leaves the received useful signal s [n] + d [n] on the output side only at the frequency of the fundamental wave ω0. The first transformation unit 13 then transforms that by means of the first filter device 12 filtered useful signal s [n] + d [n] from the time domain to the frequency domain.

Through the first filter device 12 and the downstream first transformation unit 13 Only the first interference amplitude D _w [k] at the first carrier frequency k, which is used by the charge determination signal or the teletax signal, is provided. The first transformation unit 13 leads to the provision of the first interference amplitude D _w [k] at the first carrier frequency k for the frequency transformation in particular a Görtzel algorithm by.

In contrast, the second filter device leaves 14 the received useful signal s [n] + d [n] on the output side only not at the frequency of the fundamental wave ω0 of the interference signal d [n] by. By eliminating the fundamental wave ω0 of the noise signal d [n], the leak effect is substantially avoided. In the following, the second transformation unit transforms 15 that by means of the second filter device 14 filtered useful signal s [n] + d [n] from the time domain to the frequency domain.

The subtractors 31 - 33 fulfill the analog functionality as the subtractor 3 according to 1 ,

In the fourth embodiment according to 5 represents the second filter device 14 the compensation of the leak effect safely. The compensation of the perturbations of the respective harmonics of the charge determination signal is via the path of the first filter device 12 , the first transformation unit 13 and the respective computing device 21 - 23 for the corresponding carrier frequency l, m, n ensured.

In 6 is a schematic flow diagram of a preferred embodiment of the method according to the invention shown. The method according to the invention for compensating for disturbances which are caused by a fundamental wave ω0 and harmonics i · ω0 of an interference signal, in particular a sinusoidal interference signal d [n], upon receiving a useful signal s [n] superimposed on the interference signal d [n] + d [n], has the following steps:

Process step a:

Transforming the received useful signal s [n] + d [n] from a time domain into a frequency domain to provide a plurality of complex amplitudes D _w [k], S _w [l] + D _w [l] at different carrier frequencies k, l.

Process step b:

Providing a complex first disturbance amplitude D _w [k] caused by the fundamental wave ω0 at a first carrier frequency k which is not used by the useful signal s [n].

Process step c:

Computing a complex second perturbation _amplitude A _ω0 [l] caused by the fundamental wave ω0 at a second carrier frequency l from the first perturbation amplitude D _w [k] and / or computing at least one complex third caused by the respective i-th harmonic waves i · ω0 _{Interference amplitude} A _{i · ω0} [l] at the second carrier frequency l from the first _{interference amplitude} D _w [k].

Process step d:

Subtracting the second _{interference amplitude} A _ω0 [l] and / or the respective third _interference amplitudes A _{i · ω0} [l] from the complex amplitude S _w [l] + D _w [l] of the transformed useful signal at the second carrier frequency l.

Even though the present invention above based on the preferred embodiments It is not limited to this, but in many ways and modifiable. In particular, the various embodiments the computing device and the transformation device are arbitrarily commutable. Furthermore can also be a harmonic of the interfering signal as a reference tone for the provision the second and third noise amplitudes be used.

1

transforming device

21-23

calculator

21'-23 '

calculator

3; 31-33

subtracting

41-45

calculation unit

5

Potenziervorrichtung

61-62

weighting device

7

Real field device

8th

Imaginärteilbildvorrichtung

9

multiplier

10

Phase rotation unit

11

adder

12

first filter means

13

second filter means

14

first transformation unit

15

second transformation unit

s [n]

payload in the time domain

d [n]

noise in the time domain

ω0

fundamental wave of the interference signal

i · ω0

i-th Harmonic of the interfering signal

k

first carrier frequency

l

second carrier frequency

m

third carrier frequency

n

fourth carrier frequency

c _i

weighting function

_i

weighting factor

D _w [k]

complex first interference amplitude at the first Trä

gerfrequenz (K)

D _{i · ω0}

first noise amplitude at the i-th harmonic

ĉ _i · D _{i · ω0}

weighted first interference amplitude at the i-th O

berwelle

A _ω0 [l]

complex second interference amplitude at the second

carrier frequency (L)

A _{i · ω0} [l]

complex third noise amplitude at the second

carrier frequency

A _ω0

complex fourth noise amplitude the fundamental wave (ω0)

of interference signal (D [n])

A _{i · ω0}

complex fifth noise amplitude the i th harmonic

(i · ω0) of the interfering signal (D [n])

C _i * A _{i * ω 0}

weighted, complex fifth noise amplitude the i-

th Harmonic (i · ω0) of the interfering signal (D [n])

S _w [l]

payload in the frequency domain

D _w [l]

noise in the frequency domain

Re (D _w [k])

real part the first interference amplitude in the first

carrier frequency (K)

Im (D _w [k])

Imaginary part of first interference amplitude in the

first carrier frequency (K)

a-d

step

Claims (11)

Device for compensating for disturbances caused by a fundamental wave (ω0) and at least one harmonic wave (i · ω0) of a noise signal, in particular a sinusoidal noise signal (d (n)), upon receipt of a noise signal (d [n ]) superposed useful signal (s [n] + d [n]), comprising: (a) a transformation device ( 1 ) receiving the received useful signal (s [n] + d [n]) superposed with the interfering signal (d [n]) from a time domain into a frequency domain to provide a plurality of complex amplitudes (D _w [k], S _w [l] + D _w [l]) are transformed at different carrier frequencies (k, l) and a complex first disturbing amplitude (D _w [k]) caused by the fundamental wave (ω0) at one of the useful signal (s [n]) unused first carrier frequency (k); (b) a computing device ( 21 - 23 ), which causes a complex second _{interference amplitude} (A _ω0 [l]) at a second carrier frequency (l) and / or at least one complex third interference amplitude (A _{i · ω0} [l]) at the second carrier frequency (l) is generated from the first _{interference amplitude} (D _w [k]); and (c) with a subtracting device ( 3 ), which the second _{interference amplitude} (A _ω0 [l]) and / or one or more third _interference amplitudes (A _{i · ω0} [l]) of the complex amplitude (S _w [l] + D _w [l]) of the transformed useful signal subtracted at the second carrier frequency (l). Device according to at least one of the preceding claims, characterized in that the transformation device ( 1 ) has an FFT device that receives the received signal with the interfering signal (d [n]) superimposed useful signal (s [n] + d [n]) of the time domain in the frequency domain by means of a Fourier transform, in particular a fast Fourier transform transformed. Device according to claim 1, characterized in that that with the interfering signal (d [n]) superimposed useful signal (s [n] + d [n]) by means of a discrete multitone modulation method is modulated. Device according to at least one of the preceding Claims, characterized in that the fundamental wave (ω0) of the sinusoidal noise signal (d [n]) a charge determination signal formed. Device according to at least one of the preceding claims, characterized in that the calculation device ( 21 - 23 ): - a first calculation unit ( 41 ) which _generates a complex fourth _{noise amplitude} (A _ω0 ) of the fundamental wave (ω0) of the noise signal (d [n]) from the first noise amplitude (D _w [k]) at the first carrier frequency (k); - a potentizer ( 5 ) which, by power generation or phase rotation, generates a complex fifth disturbance _amplitude (A _{i * ω 0} ) at the i-th harmonic from the generated fourth disturbance _amplitude (A _{ω 0} ) of the fundamental wave (ω 0); A first weighting device ( 61 ) weighted by weights having a weighting function (c _i ) that models a nonlinearity of an amplification unit of a transmission unit that transmits the interference signal (d [n]), a weighted complex fifth _{interference amplitude} (c _i * A _{i * ω 0} ) fifth _{noise amplitude} (A _{i · ω0} ) generated; A second calculation unit ( 42 ) which _generates the second _{noise amplitude} (A _ω0 [l]) at the second carrier frequency (I) from the fourth _{noise amplitude} (A _ω0 ) of the fundamental wave (ω0); and - a third calculation unit ( 43 ) which _generates the third disturbance _amplitude (A _{i * ω 0} [l]) at the second carrier frequency (l) from the weighted fifth disturbance amplitude (c _i * A _{i * ω 0} ). Device according to at least one of claims 1-4, characterized in that the calculation device ( 21 - 23 ): - a potentizer ( 5 ) which by power generation or phase rotation produces a first spurious amplitude (D _{i * ω 0} ) at the ith harmonic from the first _{spurious amplitude} (D _w [k]); - a fifth calculation unit ( 45 ) which generates the third disturbance _amplitude (A _{i · ω0} [l]) at the second carrier frequency (l) from the generated first disturbance _amplitude (D _{i · ω0} ) at the ith harmonic; and - a fourth calculation unit ( 44 ), which _generates the second _{interference amplitude} (A _ω0 [l]) at the second carrier frequency (l) from the first _{interference amplitude} (D _w [k]) at the first carrier frequency (k). Device according to at least one of claims 1-4, characterized in that the calculation device ( 21 - 23 ): - the exponentiation device ( 5 ) which by power generation or phase rotation produces a first spurious amplitude (D _{i * ω 0} ) at the ith harmonic from the first _{spurious amplitude} (D _w [k]); A second weighting device ( 62 ) which _generates by means of a complex weighting factor (ĉ _i ) a weighted first disturbance amplitude (ĉ _i · D _{i · ω0} ) at the ith harmonic from the first disturbance _amplitude (D _{i · ω0} ) at the i-th harmonic; A third calculation unit ( 43 ) which _generates the third disturbance _amplitude (A _{i · ω0} [l]) at the second carrier frequency (l) from the weighted first disturbance amplitude (ĉ _i · D _{i · ω0} ) at the ith harmonic; and - the fourth calculation unit ( 44 ), which _generates the second _{interference amplitude} (A _ω0 [l]) at the second carrier frequency (l) from the first _{interference amplitude} (D _w [k]) at the first carrier frequency (k). Device according to at least one of claims 5-7, characterized in that at least one of the calculation units ( 41 - 45 ): - an extracting device ( 7 . 8th ), which extracts a real part (Re (D _w [k])) as well as an imaginary part (Im (D _w [k])) from a complex interference amplitude (D _w [k]) received on the input side and provides it on the output side; A multiplier device ( 9 ) comprising a vector of the real part (Re (D _w [k])) and the imaginary part (Im (D _w [k])) of the received noise amplitude (D _w [k]) with a correction matrix (W ^-1 (k , ω0)) and corrects the received noise amplitude (D _w [k]) at a first frequency (k) to a noise amplitude at a second frequency (ω0); and - a phase rotation unit ( 10 ) which performs a phase rotation of the imaginary part (Im (D _w [k]) multiplied by the correction matrix (W ^-1 (k, ω0)); and an adding device ( 11 ) corresponding to that of the multiplying device ( 9 ) Real provided on the output side part and that of the phase rotation device ( 10 ) provided imaginary part. Device according to at least one of the preceding claims, characterized in that the transformation device ( 1 ): - a first filter device ( 12 ), which transmits the received, with the interfering signal (d [n]) superimposed useful signal (s [n] + d [n]) on the output side only at the frequency of the fundamental wave (ω0); A first transformation unit ( 13 ) superimposed on the received signal with the interfering signal (d (n)) and by means of the first filter device ( 12 ) filtered useful signal (s [n] + d [n]) transformed from the time domain into the frequency domain; A second filter device ( 14 ) which transmits the received signal (s [n] + d [n]) superposed with the interference signal (d [n]) on the output side only at the frequency of the fundamental wave (ω0) of the interference signal (d [n]); and a second transformation unit ( 15 ), which received the received, with the interference signal (d [n]) superimposed and by means of the second filter device ( 14 ) filtered useful signal (s [n] + d (n)) transformed from the time domain in the frequency domain. Method for compensating for disturbances caused by a fundamental wave (ω0) and by harmonics (i · ω0) of a noise signal, in particular a sinusoidal noise signal (d [n]), when receiving a noise signal (d [n]) superposed useful signal (s [n] + d [n]), comprising the following steps: (a) transforming the received with the interference signal (d [n]) superimposed useful signal (s [n] + d [n]) of a time range in a frequency range for providing a plurality of complex amplitudes (D _w [k], S _w [l] + D _w [l]) at different carrier frequencies (k, l); (b) providing a complex first disturbing amplitude (D _w [k]) caused by the fundamental wave (ω0) at a first carrier frequency (k) not utilized by the useful signal (s [n]); (c) calculating a complex second perturbation _amplitude (A _ω0 [l]) caused by the fundamental wave (ω0) at a second carrier frequency (l) from the first perturbation amplitude (D _w [k]) and / or calculating at least one by one of Harmonic (i · ω0) caused complex third _{interference amplitude} (A _{i · ω0} [l]) at the second carrier frequency (l) from the first _{interference amplitude} (D _w [k]); and (d) subtracting the second perturbation _amplitude (A _ω0 [l]) and / or one or more of the third perturbation amplitudes (A _{i * ω0} [l]) from the complex amplitude (S _w [l] + D _w [l]) the transformed useful signal at the second carrier frequency (l). Method according to claim 10, characterized in that with the interference signal (d [n]) superimposed User signal (s [n] + d [n]) by means of a discrete multitone modulation method is modulated.