Veröffentlichungsnummer | US20090285194 A1 |

Publikationstyp | Anmeldung |

Anmeldenummer | US 12/415,676 |

Veröffentlichungsdatum | 19. Nov. 2009 |

Eingetragen | 31. März 2009 |

Prioritätsdatum | 31. März 2008 |

Auch veröffentlicht unter | US8811917, US9768739, US20080265996, US20140327481, WO2009122298A2, WO2009122298A3 |

Veröffentlichungsnummer | 12415676, 415676, US 2009/0285194 A1, US 2009/285194 A1, US 20090285194 A1, US 20090285194A1, US 2009285194 A1, US 2009285194A1, US-A1-20090285194, US-A1-2009285194, US2009/0285194A1, US2009/285194A1, US20090285194 A1, US20090285194A1, US2009285194 A1, US2009285194A1 |

Erfinder | Wan Jong Kim, Kyoung Joon Cho, Jong Heon Kim, Shawn Patrick Stapleton |

Ursprünglich Bevollmächtigter | Dali Systems Co. Ltd. |

Zitat exportieren | BiBTeX, EndNote, RefMan |

Patentzitate (84), Referenziert von (10), Klassifizierungen (16), Juristische Ereignisse (1) | |

Externe Links: USPTO, USPTO-Zuordnung, Espacenet | |

US 20090285194 A1

Zusammenfassung

An efficient peak cancellation method for reducing the peak-to-average power ratio in wideband communication systems uses repeated clipping and frequency domain filtering to achieve a desired peak-to-average power ratio for wideband code division multiple access and orthogonal frequency division multiplexing signals. The maximum magnitude of the filtered pulse is determined by a scaling factor which permits eliminating several iterations while still achieving convergence to the targeted peak-to-average power ratio, thereby reducing computational load and saving hardware resources. This results in improved performance in terms of error vector magnitude, adjacent channel leakage ratio and peak-to-average power ratio.

Ansprüche(13)

(a) clipping a baseband input signal;

(b) subtracting the baseband input signal from the result of said step (a);

(c) noise shaping the result of step (b);

(d) scaling the result of the said step (c); and

(e) subtracting from the result of step (d) the delayed baseband input signal.

wherein α^{(i) }is a scaling factor at i-th iteration, p_{n }the clipped signal or peak cancellation signal, and pf_{n }the output signal of the noise shaper.

Beschreibung

- [0001]This application incorporates by reference and claims the benefit of U.S. Provisional Patent Application Ser. No. 61/041,164, filed Mar. 31, 2008, and having the same inventors and title as the present application
- [0002]1. Field of the Invention
- [0003]The present invention generally relates to wideband communication systems using multiplexing modulation techniques. More specifically, the present invention relates to methods for reducing the peak-to-average power ratio for wideband code division multiple access and orthogonal frequency division multiplexing signals.
- [0004]2. The Prior Art
- [0005]As a result of the increasing importance of spectral efficiency in mobile communications, effective modulation techniques, such as wideband code division multiple access (WCDMA) and orthogonal frequency division multiplexing (OFDM), have been used. These modulations have large envelope fluctuations, since the transmitted signal is generated by adding a large number of statistically independent signals. The high peak-to-average power ratio (PAPR) sets strict requirements for the linearity of the power amplifier (PA) leading to low power efficiency, since it is desirable for the PA to operate in its linear region. The use of deliberate envelope clipping to digitally distort the signal while maintaining the signal quality at a sufficient level is a simple and practical way to decrease PAPR. Moreover, the reduced PAPR via clipping gives rise to the possibility of utilizing the dynamic range of the digital-to-analog-converter (DAC) more efficiently. The various PAPR techniques can be categorized into two groups depending on whether they use linear techniques (modulation-and-coding-dependent) or nonlinear techniques (modulation-and-coding-independent). Methods that use linear techniques for OFDM systems do not distort the signal in the time domain so that the spectral properties are not altered.
- [0006]On the other hand, nonlinear techniques modify the envelope of the time domain signal and are mainly based on clipping-filtering (CF) and peak windowing (PW) clipping. The idea of the PW clipping method is to filter the clipped output signal using the window function with the coefficient weights. The windowed output signal must satisfy the inequality so as to achieve the desired clipping level. To minimize the resultant error in the time domain, the inequality must be as close to equality as possible. This is dependent on the type and length of the window. The resultant function is then multiplied by the delayed input signal [O. Vaananen, J. Vankka, and K. Halonen, “Effect of Clipping in Wideband CDMA System and Simple Algorithm for Peak Windowing,” World Wireless Congress, San Francisco, pp. 614-619, May 2002].
- [0007]To suppress peak re-growth when filtering the out-of-band distortion of the clipped signal, iterative clipping and filtering for OFDM systems have been used. This approach has suggested iterative clipping and filtering of the clipped pulses, so as to reduce the convergence rate to the targeted PAPR. However, techniques based on repeated clipping and filtering that have been implemented for OFDM systems require several iterations to converge to the desired PAPR level, which implies that it is not an efficient algorithm for hardware implementation [J. Armstrong, “Peak-to-average power reduction for OFDM by repeated clipping and frequency domain filtering,” IEE Electronics Letters, vol. 38, no. 5, pp. 246-247, February 2002], [S. H. Leung, S. M. Ju, and G. G. Bi, “Algorithm for repeated clipping and filtering in peak-to-average power reduction for OFDM,” IEE Electronics Letters, vol. 38, no. 25, pp. 1726-1727, December 2002].
- [0008]Hence, a need remains in the art for an improved method for reducing the PAPR in wideband communication systems that is able to eliminate several iterations to converge to the desired PAPR level and to simplify the hardware implementation for multi-carrier systems, such as OFDM and WCDMA.
- [0009]Accordingly, the present invention has been made in view of the above problems, and it is an object of the present invention to provide a novel efficient method of peak cancellation (PC) for reducing the PAPR for wideband communication system applications. To achieve the above objects, according to an embodiment of the present invention, the technique is based on a method of repeated clipping and filtering. While conventional repeated peak cancellation (RPC) requires several iterations so as to converge into the targeted PAPR, since filtering causes peak re-growth, the present invention is able to eliminate several iterations, which subsequently saves hardware resources by means of the proper scaling factor.
- [0010]Both the foregoing and further objects and advantages of the invention can be more fully understood from the following detailed description taken in conjunction with the accompanying drawings in which:
- [0011]
FIG. 1 . is a schematic diagram showing a multi-stage scaled repeated peak cancellation (SRPC) method. - [0012]
FIG. 2 . is a schematic diagram showing a preferred embodiment of the present invention. - [0013]
FIG. 3A . is a schematic diagram showing a noise shaper for multi-carrier. - [0014]
FIG. 3B . is a schematic diagram showing a noise shaper for single-carrier. - [0015]
FIG. 3C is a schematic diagram showing an embodiment of a clipper - [0016]
FIG. 4A . is a graph showing a peak cancellation pulse in time domain before filtering, after filtering at each stage, respectively (Prior Art). - [0017]
FIG. 4B . is a graph showing peak cancellation pulse in time domain before filtering, after filtering, and after filtering and scaling at each stage, respectively. - [0018]
FIG. 5 . is a graph showing simulation results of the PAPR versus EVM for four WCDMA carriers using just clipping method, the PW method and the SRPC method of the present invention respectively. - [0019]
FIG. 6 . is a graph showing simulation results of the ACLR versus PAPR for four WCDMA carriers using the PW method, the RPC method, and the SRPC method of the present invention respectively. - [0020]
FIG. 7 . is a table showing performance comparisons of simulation results of the RMS EVM for different number of WCDMA carriers using the PW method, the RPC method, and the SRPC method of the present invention respectively. - [0021]
FIG. 8 . is a graph showing simulation results of the PDF for four WCDMA carriers using the SRPC method of the present invention respectively. - [0022]The conventional repeated peak cancellation (RPC) method can effectively reduce the PAPR. However, the RPC method requires several iterations to converge to the desired PAPR level, which implies that it is not an efficient algorithm for hardware implementation. Instead, the present invention applies a scaling factor to the peak cancellation pulse after the noise shaper but inside the peak cancellation loop. The objective is to achieve fewer iterations during processing and thereby reduce the PAPR and EVM. Compared to the conventional RPC method, an embodiment of the present invention achieves lower PAPR for, for example, four WCDMA carriers although approach is expandable into an unlimited number of carriers. The method provided by the present invention is therefore referred to hereinafter as Scaled Repeated Peak Cancellation (SRPC).
- [0023]Various embodiments of the SRPC method according to the present invention are described in detail below with reference to the accompanying drawings.
- [0024]
FIG. 1 . is a schematic diagram showing an embodiment of the multi-stage SRPC method. As illustrated, the baseband signal x(n)**101**goes through the first SPC**102**with a scaling factor α^{(0) }**107**, and z_{n}^{(1) }**105**is the output from the first iteration of the peak cancellation. After the i-th iteration, the resulting signal can be represented by Z**110**. - [0025]In the SRPC method of the present invention, as illustrated in
FIG. 2 , the baseband signal x(n)**201**first passes through the clipper**202**. The clipper**202**output, c_{n}, can be written as follows: - [0000]
${c}_{n}=\{\begin{array}{cc}\frac{A}{\uf603{x}_{n}\uf604},& \uf603{x}_{n}\uf604>A\\ 1,& \uf603{x}_{n}\uf604\le A\end{array}$ - [0026]where A is the clipping threshold level. The clipped pulse or peak cancellation pulse, p
_{n }can be written as - [0000]

*p*_{n}*=x*_{n}*−x*_{n}*·c*_{n } - [0027]Finally the PAPR reduced signal, z
_{n }**212**is described by - [0000]
$\begin{array}{c}{z}_{n}=\ue89e{x}_{n-d}-\alpha \xb7{\mathrm{pf}}_{n}\\ =\ue89e{x}_{n-d}-\alpha \xb7{p}_{n}\star {h}_{n}\end{array}$ - [0000]where pf
_{n}, h_{n}, and α denote the output signal of the noise shaper**206**, the impulse response of the low pass filter (LPF), and the scaler**208**, respectively. * denotes the convolution operation. - [0028]As shown in
FIG. 3 *a*for multi-carrier operation, the peak cancellation pulse**301**is frequency translated by (On), filtered, frequency translated back to baseband and combined. This is because the out-of-band emissions reside between the different carriers and cannot be filtered out by line pass filter**304**, as opposed to the single carrier applications inFIG. 3 *b*where only one finite impulse response (FIR) filter**304**can be used. The FIR filters**304**for the multi-carriers have the same coefficients as that of a signal carrier FIR filter**304**. There is peak re-growth beyond the clipped signal. This occurs because the resultant peak cancellation pulse (p_{n})**301**is filtered by the noise shaper and subsequently subtracted from the delayed input signal. This has the net effect of increasing the peaks beyond that of the clipped signal. Let z_{n }**212**be the output signal and z_{n}^{(1) }**105**be the output from the first iteration. After the i-th iteration, the resulting signal**110**can be represented by - [0000]
${z}_{n}^{\left(2\right)}={z}_{n}^{\left(0\right)}-{\alpha}^{\left(1\right)}\xb7{\mathrm{pf}}_{n}^{\left(1\right)}$ $\begin{array}{c}{z}_{n}^{\left(3\right)}=\ue89e{z}_{n}^{\left(2\right)}-{\alpha}^{\left(2\right)}\xb7{\mathrm{pf}}_{n}^{\left(2\right)}\\ =\ue89e{z}_{n}^{\left(0\right)}-{\alpha}^{\left(1\right)}\xb7{\mathrm{pf}}_{n}^{\left(1\right)}-{\alpha}^{\left(2\right)}\xb7{\mathrm{pf}}_{n}^{\left(2\right)}\end{array}$ $\vdots $ $\begin{array}{c}{z}_{n}^{\left(i\right)}=\ue89e{z}_{n}^{\left(i-1\right)}-{\alpha}^{\left(i\right)}\xb7{\mathrm{pf}}_{n}^{\left(i\right)}\\ =\ue89e{z}_{n}^{\left(0\right)}-\sum _{j=1}^{i}\ue89e{\alpha}^{\left(j\right)}\xb7{\mathrm{pf}}_{n}^{\left(j\right)}\end{array}$ - [0029]The scaler, α
^{(i)},**109**, at i-th iteration can be calculated as - [0000]
${\alpha}^{\left(i\right)}=\frac{\mathrm{max}\ue8a0\left(\uf603{p}_{m}^{\left(i\right)}\uf604\right)}{\mathrm{max}\ue8a0\left(\uf603{\mathrm{pf}}_{n}^{\left(i\right)}\uf604\right)}$ - [0030]The envelope of the input signal has a Rayleigh distribution according to the central limit theorem, so that the maximum magnitude of the clipping pulse can be numerically found once the threshold level is set. This implies that the maximum magnitude of the filtered pulse can be accordingly determined.
- [0031]Referring next to
FIG. 3C , an embodiment of a clipper in accordance with the invention is shown in schematic block diagram form. In the embodiment shown, a clipper comprises an amplitude calculator**325**which receives the input signal and provides it to a comparator**327**and a lookup table (LUT)**329**. A clipping threshold signal**331**, which can be preset or variable according to the desired implementation, provides a second input to the second input to the comparator**327**, and also provides an input to a multiplier**333**. The output of the LUT provides the second input to the multiplier, the output of which is provided to a mux**335**. The output of the comparator**327**provides a “select” input to the mux**335**, while a constant**337**provides the second signal input to the mux. Thus, it can be appreciated that the mux selects either the output of the multiplier or a constant, depending on the comparison between the amplitude of the input signal and the clipping threshold. It will be appreciated by those skilled in the art that numerous alternatives and equivalents to the embodiment ofFIG. 3C can be constructed given the teachings herein, and the illustrated embodiment is therefore not intended to be limiting and is just one of many that perform the requisite clipping function. - [0032]
FIGS. 4 *a*and**4***b*represent peak cancellation pulses in the time domain for the prior art and the present invention, respectively. As shown inFIG. 4 *b*, applying the scaling factor results in less iteration when compared toFIG. 4 *a*. Therefore, this scaling factor significantly reduces the computational load, which saves hardware resources in an implementation. According to numerical simulations, it has been found that two or three iterations of the SRPC is sufficient. - [0033]In examining the performance of an embodiment of the SRPC method, 3
^{rd }Generation Partnership Project (3GPP) standard specifications state that the EVM and ACLR at 5 MHz offset should be less than 17.5% and −45 dBc, respectively. The scrambling codes and the time offsets of the time slot duration for multi-carriers test model 1 (TM1) of the WCDMA downlink system is based on 3GPP TS 25.141, Section 6.1.1 of Release 6 (2002-12). The numerical simulations used a signal that is TM1 with 64 dedicated physical channels (DPCH) and 614,400 input samples (one radio frame at 61.44 Msamples/sec) that are processed in MATLAB. A low pass FIR filter with 129 taps was designed to meet out-of-band distortions specifications of −77 dBc. - [0034]
FIG. 5 . is a graph showing simulation results of the PAPR with respect to EVM for four WCDMA carriers using the peak windowing method with an 85 tap Hamming window length, just clipping, and an embodiment of the present invention's SRPC method with three stages of the present invention respectively, through which the performance of the PAPR reduction of the three methods can be compared. In the figure, the solid line with diamond markers represents the performance with just clipping; this sets the lower bound on the PAPR and EVM. It obviously has a large out-of-band spectral radiation. The three-stage PC compressed the PAPR by 0.8 dB more than the single stage at an EVM of 10%. Using the SRPC technique, the PAPR can be suppressed to approximately 5.7 dB at a fixed 10% of EVM after only three stages, while 6.7 dB is achievable with the PW method based on four WCDMA carrier input signal. It should be noted that even a single stage of the proposed algorithm outperforms the PW technique and it requires only two iterations to obtain the same performance that is achieved by seven iterations of the conventional RPC method. - [0035]
FIG. 6 . is a graph showing simulation results of the ACLR versus PAPR for four WCDMA carriers using the peak windowing method, the conventional RPC method, and the SRPC method of the present invention respectively. In the figure, the PW technique has a critical disadvantage that degrades ACLR as opposed to conventional RPC and SRPC method. The original input signal has an ACLR of approximately −77 dBc. Another point to note is that the conventional RPC and SRPC methods deteriorate the ACLR up to approximately 2 dB as the clipping threshold is reduced. This is a result of the decrease in the average power as clipping becomes more significant. - [0036]
FIG. 7 . is a table showing performance comparisons of simulation results of the RMS EVM for different numbers of WCDMA carriers using the PW method, the RPC method, and the SRPC method of the present invention respectively. Simulations were performed for a different number of carriers. For a single carrier, all three techniques represent a similar ability in terms of EVM and PAPR. However, the PW method still allows the ACLR to be compromised, unlike the other two methods. The conventional RPC method requires more than five iterations which increase its complexity, while the proposed SRPC method only requires two iterations. It is not possible for the PW method to achieve a PAPR of 5.5 dB, for the three carrier and four carrier cases, even without considering EVM and ACLR. This is because the window significantly alters many input samples due to the large clipping, which significantly changes the average power. - [0037]
FIG. 8 . is a graph showing simulation results of the PDF for four WCDMA carriers using the SRPC method of the present invention respectively. In the figure, the solid line shows the PDF of the original input signal and the PDF at each stage of three stage SRPC method is illustrated. The PDF difference can be minimized in the region of samples with magnitude less than 1 V, as illustrated inFIG. 8 . - [0038]In summary, the SRPC method of the present invention, compared to the conventional RPC method, could reduce PAPR more effectively since the SRPC method is able to eliminate several iterations, which subsequently saves hardware resources. In four WCDMA carriers, the present invention could achieve the state of the art performance for WCDMA applications.
- [0039]Although the present invention has been described with reference to the preferred embodiments, it will be understood that the invention is not limited to the details described thereof. Various substitutions and modifications have been suggested in the foregoing description, and others will occur to those of ordinary skill in the art. Therefore, all such substitutions and modifications are intended to be embraced within the scope of the invention as defined in the appended claims.

Patentzitate

Zitiertes Patent | Eingetragen | Veröffentlichungsdatum | Antragsteller | Titel |
---|---|---|---|---|

US4700151 * | 19. März 1986 | 13. Okt. 1987 | Nec Corporation | Modulation system capable of improving a transmission system |

US4929906 * | 23. Jan. 1989 | 29. Mai 1990 | The Boeing Company | Amplifier linearization using down/up conversion |

US5049832 * | 20. Apr. 1990 | 17. Sept. 1991 | Simon Fraser University | Amplifier linearization by adaptive predistortion |

US5396190 * | 30. März 1994 | 7. März 1995 | Mitsubishi Denki Kabushiki Kaisha | Circuit for compensating for nonlinear distortion in transmit power amplifier |

US5486789 * | 28. Febr. 1995 | 23. Jan. 1996 | Motorola, Inc. | Apparatus and method for providing a baseband digital error signal in an adaptive predistorter |

US5579342 * | 22. Sept. 1994 | 26. Nov. 1996 | Her Majesty The Queen In Right Of Canada As Represented By The Minister Of Communications | Pre-compensated frequency modulation (PFM) |

US5675287 * | 12. Febr. 1996 | 7. Okt. 1997 | Motorola, Inc. | Digital DC correction circuit for a linear transmitter |

US5678198 * | 15. Mai 1995 | 14. Okt. 1997 | Southwestern Bell Technology Resources, Inc. | System for controlling signal level at both ends of a transmission link, based upon a detected value |

US5732333 * | 14. Febr. 1996 | 24. März 1998 | Glenayre Electronics, Inc. | Linear transmitter using predistortion |

US5757229 * | 28. Juni 1996 | 26. Mai 1998 | Motorola, Inc. | Bias circuit for a power amplifier |

US5786728 * | 27. Juni 1996 | 28. Juli 1998 | Nokia Mobile Phones, Ltd. | Cuber based predistortion circuit and mobile station using the same |

US5936464 * | 3. Nov. 1997 | 10. Aug. 1999 | Motorola, Inc. | Method and apparatus for reducing distortion in a high efficiency power amplifier |

US5937011 * | 26. März 1996 | 10. Aug. 1999 | Airnet Communications Corp. | Multi-carrier high power amplifier using digital pre-distortion |

US5949283 * | 29. Juni 1998 | 7. Sept. 1999 | Spectrian | Adaptive digital predistortion linearization and feed-forward correction of RF power amplifier |

US5959499 * | 30. Sept. 1997 | 28. Sept. 1999 | Motorola, Inc. | Predistortion system and method using analog feedback loop for look-up table training |

US6054896 * | 17. Dez. 1998 | 25. Apr. 2000 | Datum Telegraphic Inc. | Controller and associated methods for a linc linear power amplifier |

US6055418 * | 3. Juli 1997 | 25. Apr. 2000 | Thomcast Communications, Inc. | Computer program product configured to control modular transmission system components |

US6091941 * | 16. Nov. 1998 | 18. Juli 2000 | Fujitsu Limited | Radio apparatus |

US6240144 * | 6. Aug. 1999 | 29. Mai 2001 | Samsung Electronics Co., Ltd. | Apparatus and method of linearizing a power amplifier in a mobile radio communication system |

US6242979 * | 23. Febr. 2000 | 5. Juni 2001 | Motorola, Inc. | Linearization using parallel cancellation in linear power amplifier |

US6246865 * | 4. Febr. 1997 | 12. Juni 2001 | Samsung Electronics Co., Ltd. | Device and method for controlling distortion characteristic of predistorter |

US6275685 * | 10. Dez. 1998 | 14. Aug. 2001 | Nortel Networks Limited | Linear amplifier arrangement |

US6301579 * | 20. Okt. 1998 | 9. Okt. 2001 | Silicon Graphics, Inc. | Method, system, and computer program product for visualizing a data structure |

US6400774 * | 9. Dez. 1998 | 4. Juni 2002 | Matsushita Electric Industrial Co., Ltd. | Nonlinearity-caused distortion compensating system |

US6424225 * | 27. Nov. 2000 | 23. Juli 2002 | Conexant Systems, Inc. | Power amplifier circuit for providing constant bias current over a wide temperature range |

US6512417 * | 11. Mai 2001 | 28. Jan. 2003 | Nortel Networks Limited | Linear amplifier arrangement |

US6552634 * | 2. Okt. 2000 | 22. Apr. 2003 | Frederick Herbert Raab | Wideband, minimum-rating filters and multicouplers for power amplifiers |

US6625429 * | 30. Juni 2000 | 23. Sept. 2003 | Nec Corporation | Mobile radio communication apparatus |

US6639050 * | 12. Apr. 2000 | 28. Okt. 2003 | Ohio University | Synthetic genes for plant gums and other hydroxyproline-rich glycoproteins |

US6677870 * | 21. Febr. 2002 | 13. Jan. 2004 | Solid Technologies, Inc. | Device and method for compensating for nonlinearity of power amplifier with predistortion in IF band |

US6697436 * | 19. Juni 2000 | 24. Febr. 2004 | Pmc-Sierra, Inc. | Transmission antenna array system with predistortion |

US6703897 * | 26. Dez. 2001 | 9. März 2004 | Nortel Networks Limited | Methods of optimising power amplifier efficiency and closed-loop power amplifier controllers |

US6741663 * | 27. Okt. 2000 | 25. Mai 2004 | Nokia Corporation | Linearization method for amplifier, and amplifier arrangement |

US6747649 * | 19. März 2002 | 8. Juni 2004 | Aechelon Technology, Inc. | Terrain rendering in a three-dimensional environment |

US6751447 * | 30. Dez. 1999 | 15. Juni 2004 | Samsung Electronics Cop., Ltd. | Adaptive digital pre-distortion circuit using output reference signal and method of operation |

US6781951 * | 22. Okt. 1999 | 24. Aug. 2004 | Koninklijke Philips Electronics N.V. | Radio communication system |

US6895704 * | 13. Nov. 2003 | 24. Mai 2005 | Hni Technologies Inc. | Work board assembly |

US6983025 * | 11. Apr. 2001 | 3. Jan. 2006 | Tropian, Inc. | High quality power ramping in a communications transmitter |

US6985704 * | 1. Mai 2002 | 10. Jan. 2006 | Dali Yang | System and method for digital memorized predistortion for wireless communication |

US7035345 * | 8. Juni 2001 | 25. Apr. 2006 | Polyvalor S.E.C. | Adaptive predistortion device and method using digital receiver |

US7042287 * | 23. Juli 2003 | 9. Mai 2006 | Northrop Grumman Corporation | System and method for reducing dynamic range and improving linearity in an amplication system |

US7061314 * | 15. Dez. 2003 | 13. Juni 2006 | Youngwoo Kwon | High linearity doherty communication amplifier with phase control |

US7064606 * | 5. März 2004 | 20. Juni 2006 | Andrew Corporation | High efficiency amplifier and method of designing same |

US7079818 * | 12. Febr. 2002 | 18. Juli 2006 | Broadcom Corporation | Programmable mutlistage amplifier and radio applications thereof |

US7102442 * | 28. Apr. 2004 | 5. Sept. 2006 | Sony Ericsson Mobile Communications Ab | Wireless terminals, methods and computer program products with transmit power amplifier input power regulation |

US7103329 * | 25. Okt. 2001 | 5. Sept. 2006 | Rockwell Collins, Inc. | Adaptive feedback channel for radio frequency power amplifiers |

US7104310 * | 27. Dez. 2004 | 12. Sept. 2006 | Hunter Automated Machinery Corporation | Mold making machine with separated safety work zones |

US7106806 * | 27. Juni 2000 | 12. Sept. 2006 | Andrew Corporation | Reducing distortion of signals |

US7109792 * | 17. Sept. 2003 | 19. Sept. 2006 | Andrew Corporation | Table-based pre-distortion for amplifier systems |

US7109998 * | 3. Okt. 2001 | 19. Sept. 2006 | Sun Microsystems, Inc. | Stationary semantic zooming |

US7151913 * | 30. Juni 2003 | 19. Dez. 2006 | M/A-Com, Inc. | Electromagnetic wave transmitter, receiver and transceiver systems, methods and articles of manufacture |

US7158765 * | 31. Juli 2001 | 2. Jan. 2007 | Agere Systems, Inc. | Method and apparatus for controlling power of a transmitted signal |

US7193472 * | 28. Febr. 2005 | 20. März 2007 | Mitsubishi Denki Kabushiki Kaisha | Power amplifier |

US7248642 * | 5. Febr. 2002 | 24. Juli 2007 | Andrew Corporation | Frequency-dependent phase pre-distortion for reducing spurious emissions in communication networks |

US7321636 * | 9. Mai 2002 | 22. Jan. 2008 | Magnolia Broadband Inc. | Communication device with smart antenna using a quality-indication signal |

US7372918 * | 30. Sept. 2004 | 13. Mai 2008 | Infineon Technologies Ag | Transmission device with adaptive digital predistortion, transceiver with transmission device, and method for operating a transmission device |

US7469491 * | 14. Dez. 2004 | 30. Dez. 2008 | Crestcom, Inc. | Transmitter predistortion circuit and method therefor |

US7831221 * | 13. Dez. 2005 | 9. Nov. 2010 | Andrew Llc | Predistortion system and amplifier for addressing group delay modulation |

US20020034260 * | 14. Sept. 2001 | 21. März 2002 | Lg Electronics Inc. | Adaptive predistortion transmitter |

US20020044014 * | 5. Juli 2001 | 18. Apr. 2002 | Wright Andrew S. | Amplifier measurement and modeling processes for use in generating predistortion parameters |

US20020080891 * | 21. Dez. 2001 | 27. Juni 2002 | Lg Electronics | Base station transmitter having digital predistorter and predistortion method thereof |

US20020101937 * | 26. Juni 1998 | 1. Aug. 2002 | Franklin P. Antonio | Predistortion technique for high power amplifiers |

US20020101938 * | 15. Juni 2001 | 1. Aug. 2002 | Masato Horaguchi | Predistortion type distortion compensation apparatus |

US20020179830 * | 1. Nov. 2001 | 5. Dez. 2002 | Pearson Robert M. | Halbach Dipole magnet shim system |

US20020187761 * | 21. Febr. 2002 | 12. Dez. 2002 | Solid Technologies, Inc. | Device and method for compensating for nonlinearity of power amplifier with redistortion in if band |

US20020193085 * | 15. Juni 2001 | 19. Dez. 2002 | Telefonaktiebolaget Lm Ericsson | Systems and methods for amplification of a communication signal |

US20030095608 * | 16. Nov. 2001 | 22. Mai 2003 | Koninklijke Philips Electronics N.V. | Transmitter with transmitter chain phase adjustment on the basis of pre-stored phase information |

US20030179829 * | 19. März 2002 | 25. Sept. 2003 | Motorola, Inc. | Method and apparatus using base band transformation to improve transmitter performance |

US20030179830 * | 25. März 2002 | 25. Sept. 2003 | Eidson Donald B. | Efficient, high fidelity transmission of modulation schemes through power-constrained remote relay stations by local transmit predistortion and local receiver feedback |

US20030207680 * | 1. Mai 2002 | 6. Nov. 2003 | Dali Yang | System and method for digital memorized predistortion for wireless communication |

US20040017859 * | 12. Nov. 2002 | 29. Jan. 2004 | Sills James A. | Transmitter with limited spectral regrowth and method therefor |

US20040057533 * | 23. Sept. 2002 | 25. März 2004 | Kermalli Munawar Hussein | System and method for performing predistortion at intermediate frequency |

US20040240585 * | 12. Juni 2002 | 2. Dez. 2004 | John Bishop | Time alignment of signals |

US20050079834 * | 30. Nov. 2004 | 14. Apr. 2005 | Toru Maniwa | Table reference type predistorter |

US20050159117 * | 22. Febr. 2005 | 21. Juli 2005 | Igor Bausov | Class-L power-output amplifier |

US20050190857 * | 23. Febr. 2005 | 1. Sept. 2005 | Braithwaite Richard N. | Digital predistortion system and method for linearizing an RF power amplifier with nonlinear gain characteristics and memory effects |

US20050262498 * | 20. Mai 2004 | 24. Nov. 2005 | Ferguson Alan L | Systems and methods for remotely modifying software on a work machine |

US20060012426 * | 14. Juli 2004 | 19. Jan. 2006 | Raytheon Company | Performing remote power amplifier linearization |

US20060270366 * | 24. Mai 2005 | 30. Nov. 2006 | Dmitriy Rozenblit | Dual voltage regulator for a supply voltage controlled power amplifier in a closed power control loop |

US20070075780 * | 5. Okt. 2005 | 5. Apr. 2007 | Enver Krvavac | Apparatus and method for adaptive biasing of a Doherty amplifier |

US20070140101 * | 15. Dez. 2005 | 21. Juni 2007 | Nortel Networks Limited | System and method for reducing peak-to-average power ratio in orthogonal frequency division multiplexing signals using reserved spectrum |

US20070171234 * | 17. Nov. 2006 | 26. Juli 2007 | Roger Crawfis | System and method for asynchronous continuous-level-of-detail texture mapping for large-scale terrain rendering |

US20070241812 * | 30. Apr. 2007 | 18. Okt. 2007 | Dali Systems Co. Ltd. | High efficiency linearization power amplifier for wireless communication |

USRE42287 * | 9. Okt. 2003 | 12. Apr. 2011 | Pixar | Stochastic level of detail in computer animation |

Referenziert von

Zitiert von Patent | Eingetragen | Veröffentlichungsdatum | Antragsteller | Titel |
---|---|---|---|---|

US8324953 * | 21. Okt. 2009 | 4. Dez. 2012 | Vyycore Ltd. | Method and a system for signal processing |

US9179321 | 8. Aug. 2013 | 3. Nov. 2015 | Axell Wireless Ltd. | Digital capacity centric distributed antenna system |

US9367828 | 26. Nov. 2013 | 14. Juni 2016 | Commscope Technologies Llc | Forward-path digital summation in digital radio frequency transport |

US9385797 | 26. Nov. 2013 | 5. Juli 2016 | Commscope Technologies Llc | Flexible, reconfigurable multipoint-to-multipoint digital radio frequency transport architecture |

US9706603 | 3. Okt. 2014 | 11. Juli 2017 | Commscope Technologies Llc | Systems and methods for noise floor optimization in distributed antenna system with direct digital interface to base station |

US9712343 | 17. Juni 2016 | 18. Juli 2017 | Andrew Wireless Systems Gmbh | Scalable telecommunications system |

US9750082 | 3. Okt. 2014 | 29. Aug. 2017 | Commscope Technologies Llc | Systems and methods for noise floor optimization in distributed antenna system with direct digital interface to base station |

US9787457 | 3. Okt. 2014 | 10. Okt. 2017 | Commscope Technologies Llc | Systems and methods for integrating asynchronous signals in distributed antenna system with direct digital interface to base station |

US9794791 | 14. Sept. 2015 | 17. Okt. 2017 | Axell Wireless Ltd. | Digital capacity centric distributed antenna system |

WO2016122204A1 * | 27. Jan. 2016 | 4. Aug. 2016 | 삼성전자 주식회사 | Method and device for controlling power in multi-carrier communication system |

Klassifizierungen

US-Klassifikation | 370/342, 370/310 |

Internationale Klassifikation | H04B7/216, H04B7/00 |

Unternehmensklassifikation | H03F2201/3224, H03F3/24, H03F1/3258, H03F1/3247, H03F3/20, H03F3/19, H03F2201/3227, H03F2200/451, H03F2201/3233, H03F2200/129 |

Europäische Klassifikation | H03F1/32P2, H03F3/24 |

Juristische Ereignisse

Datum | Code | Ereignis | Beschreibung |
---|---|---|---|

12. Aug. 2009 | AS | Assignment | Owner name: DALI SYSTEMS CO. LTD., CAYMAN ISLANDS Free format text: ASSIGNMENT OF ASSIGNORS INTEREST;ASSIGNORS:KIM, WAN JONG;CHO, KYOUNG JOON;KIM, JONG HEON;AND OTHERS;REEL/FRAME:023092/0568;SIGNING DATES FROM 20090522 TO 20090717 |

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