WO2000035160A1 - Qam modulator for radio communications - Google Patents
Qam modulator for radio communications Download PDFInfo
- Publication number
- WO2000035160A1 WO2000035160A1 PCT/US1999/024332 US9924332W WO0035160A1 WO 2000035160 A1 WO2000035160 A1 WO 2000035160A1 US 9924332 W US9924332 W US 9924332W WO 0035160 A1 WO0035160 A1 WO 0035160A1
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- WO
- WIPO (PCT)
- Prior art keywords
- digits
- power
- combining
- output
- amplifier
- Prior art date
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Classifications
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- H—ELECTRICITY
- H04—ELECTRIC COMMUNICATION TECHNIQUE
- H04L—TRANSMISSION OF DIGITAL INFORMATION, e.g. TELEGRAPHIC COMMUNICATION
- H04L27/00—Modulated-carrier systems
- H04L27/18—Phase-modulated carrier systems, i.e. using phase-shift keying
- H04L27/20—Modulator circuits; Transmitter circuits
- H04L27/2032—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner
- H04L27/2053—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases
- H04L27/206—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers
- H04L27/2067—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers with more than two phase states
- H04L27/2071—Modulator circuits; Transmitter circuits for discrete phase modulation, e.g. in which the phase of the carrier is modulated in a nominally instantaneous manner using more than one carrier, e.g. carriers with different phases using a pair of orthogonal carriers, e.g. quadrature carriers with more than two phase states in which the data are represented by the carrier phase, e.g. systems with differential coding
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F1/00—Details of amplifiers with only discharge tubes, only semiconductor devices or only unspecified devices as amplifying elements
- H03F1/02—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation
- H03F1/0205—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers
- H03F1/0294—Modifications of amplifiers to raise the efficiency, e.g. gliding Class A stages, use of an auxiliary oscillation in transistor amplifiers using vector summing of two or more constant amplitude phase-modulated signals
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- H—ELECTRICITY
- H03—ELECTRONIC CIRCUITRY
- H03F—AMPLIFIERS
- H03F3/00—Amplifiers with only discharge tubes or only semiconductor devices as amplifying elements
- H03F3/20—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers
- H03F3/24—Power amplifiers, e.g. Class B amplifiers, Class C amplifiers of transmitter output stages
Definitions
- This invention relates to modulation systems and methods and more particularly to systems and methods that can efficiently modulate a signal onto a radio frequency carrier.
- Modulation systems and methods are widely used in transmitters to modulate information including voice and/or data onto a carrier.
- the carrier may be a final carrier or an intermediate carrier.
- the carrier frequency can be in UHF, VHF, RF, microwave or any other frequency band.
- Modulators are also referred to as “mixers” or “multipliers”. For example, in a mobile radiotelephone, a modulator is used in the radiotelephone transmitter.
- Quadrature Amplitude Modulated signals are generated from data bits by using a first Quadrature Phase Shift Keying (QPSK) modulator for encoding a first pair of the data bits into one of four carrier signal phases, thereby producing a first QPSK signal.
- QPSK Quadrature Phase Shift Keying
- a second QPSK modulator encodes a second pair of the data bits into one of four carrier signal phases, thereby producing a second QPSK signal.
- the first QPSK signal is amplified to a first power level
- the second QPSK signal is amplified to a second power level.
- the first and second amplified signals are then combined to produce a signal in which four data bits are encoded.
- Offset Quadrature Phase Shift Keying may be used in place of the first and second QPSK modulators, so that an Offset Quadrature Amplitude Modulation (OQAM) transmitter is formed.
- An OQPSK modulator encodes data bits by encoding a first sub-group of the data bits into a real part of a complex signal at an odd instant of a clock, and by encoding a second sub-group of the data bits into an imaginary part of the complex signal at an even instant of the clock.
- OQPSK modulation provides the benefit of having all signal transitions being constrained to trajectories around constant radius circles, thereby producing spectral efficiency. See the '531 patent abstract.
- a respective phase control symbol is then used to control the phase of an output signal at the radio carrier frequency from a respective one of the plurality of power amplifiers.
- Each of the power amplifiers provides an output power level that is related to the numerical significance of the first and second digits that form the associated phase control symbol.
- the output power levels of the plurality of power amplifiers are combined to thereby form the modulated radio power signal.
- the digits are binary digits such that each of the phase control symbols is one of four values.
- the power amplifiers are preferably saturated power amplifiers that produce a constant radio frequency voltage output. More preferably, the power amplifiers are bilateral power amplifiers that allow current to flow from and to an amplifier power supply.
- the output levels of the plurality of power amplifiers may be combined using various techniques. For example, a respective output power level may be applied to a primary winding of a respective one of a plurality of transformers, the secondary windings of which are serially coupled to produce the modulated radio power signal. Alternatively, a respective output power level may be applied to a respective quarter wave transmission line, and the quarter wave transmission lines may be coupled to one another to produce the modulated radio power signal. In yet another alternative, at least two of the phase control signals of the least numerical significance may be coupled to at least one linear amplifier to produce a linear output. The linear output and the output power levels of the plurality of power amplifiers may then be combined to form the modulated radio power signal.
- a real part of each of the complex numbers is represented as a plurality of first digits of decreasing numerical significance and an imaginary part of each of the complex numbers is represented as a plurality of second digits of decreasing numerical significance.
- a plurality of phase modulators is provided, a respective one of which is responsive to a respective one of the plurality of first digits and a respective one of the plurality of second digits of like numerical significance, and to the radio carrier frequency, to produce a phase modulated output at the radio carrier frequency.
- a plurality of power amplifiers is provided, a respective one of which amplifies a respective one of the phase modulated outputs of the phase modulators to an amplifier power level at an output thereof.
- a combining circuit combines the outputs of the power amplifiers according to a combining ratio to produce the modulated radio power signal. Either the amplifier output level or the combining ratio or both are selected such that the modulated radio power signal is related to the numerical significance of the plurality of first and second digits.
- each of the power amplifiers produces the same amplifier output level and the combining ratio is selected such that the outputs of the power amplifiers are combined according to a ratio that is related to the numerical significance of the digits that are associated with the respective power amplifier.
- the combining ratio is unity and the amplifier output level of a respective power amplifier is related to the numerical significance of the digits that are associated therewith.
- both the amplifier output level and combining ratio are selected such that the modulated radio power signal is related to the numerical significance of the plurality of first and second digits.
- the combining circuit may comprise a plurality of transformers, each having a primary winding and a secondary winding. A respective primary winding is coupled to a respective power amplifier.
- the plurality of secondary windings are serially coupled to produce the modulated radio power signal.
- the combining circuit may comprise a plurality of quarter wave length transmission lines, a respective one of which is coupled between a respective power amplifier and an output node to produce the modulated radio power signal at the output node.
- the digits preferably are binary digits such that each of the phase modulated outputs has one of four values.
- the power amplifiers are preferably saturated power amplifiers that produce a constant radio frequency voltage output at the amplifier power level. More preferably, the power amplifiers are bilateral power amplifiers that allow current flow from and to an amplifier power supply.
- At least one linear amplifier may be provided that is associated with at least two of the first and second digits of least numerical significance, to generate a linear output voltage at an output thereof that is proportional to combined values of the at least two of the first and second digits of least numerical significance.
- the combiner combines the output of the at least one linear amplifier and the outputs of the power amplifiers.
- the present invention can convert the stream of complex numbers representing a desired modulation of a radio signal into a modulated radio power signal at a radio carrier frequency at high efficiency. Reduced size, cost and/or power consumption of a mobile radiotelephone or other transmitter may be obtained. Power modulation systems and methods may be provided.
- Figure 1 is a block diagram illustrating systems and methods for converting a stream of complex numbers into a modulated radio power signal at a radio carrier frequency according to the present invention.
- Figures 2 and 3 are block diagrams illustrating systems and methods for converting a stream of complex numbers into a modulated radio power signal using respective first and second embodiments of combining circuits according to the present invention.
- Figure 4 is a block diagram of an embodiment of a phase modulator of Figures 1-3.
- Figure 5 graphically illustrates forming an instantaneous signal vector by adding three signal vectors according to the present invention.
- the present invention may be embodied as systems (apparatus) or methods.
- the present invention may take the form of an entirely hardware embodiment or an embodiment combining software and hardware aspects. Accordingly, individual blocks and combinations of block in the drawings support combinations of means for performing the specified functions and combinations of steps for performing the specified functions.
- Each of the blocks of the drawings, and combinations of blocks of the drawings may be embodied in many different ways, as is well known to those of skill in the art.
- a plurality of radio frequency power amplifiers that operate efficiently at successively diminishing saturated power levels, have their outputs combined such that substantially the same current waveform flows in the output power amplifier devices of all amplifiers.
- the combined signal is output to a load, such as an antenna, preferably via suitable harmonic suppression filtering.
- the drive signal to each amplifier is provided by the output of an associated phase modulator.
- Each phase modulator selects one of four output phase values, preferably spaced at 90° intervals around the full 360° circle. Phase filtering can provide smooth transition between successive phase values.
- Selection of one of the four phases is determined, for each phase modulator, by a pair of bits, one bit determining the sign of the cosine of the phase value and the other bit determining the sign of the sine of the phase value.
- the cosine sign- determining bits for all phase modulators form a binary word numerically representative of the real part of a desired transmitted complex vector while the sine sign-determining bits form the imaginary part.
- a processor such as a digital signal processor computes successive complex vectors at a given sampling rate, the succession of vectors defining a complex modulation waveform representative of an information signal to be modulated.
- Each complex vector includes a real numerical part and an imaginary numerical part having a plurality of bits at least equal to the plurality of phase modulators.
- the real and imaginary parts are applied to the plurality of phase modulators by connecting one real bit and one imaginary bit to each modulator.
- a common RF carrier signal is also supplied to each modulator.
- the combined power amplifiers produce a modulated RF power signal into the load bearing the desired informational modulation, with high conversion efficiency from the DC power source to RF power into the load.
- each successive new complex vector's real part may be applied to the modulators at alternate instants of a sampling clock while new imaginary parts are applied at the intervening instants.
- each phase value may only change by +90° or -90° between instants of the sampling clock.
- Phase transitions may then be smoothed, for each modulator, with the aid of a phase locked loop.
- the amplifiers are combined with the aid of isolating transformers that allow the amplifier output signals to be effectively connected in series with the load.
- the amplifiers are combined by quarter wavelength transmission lines.
- a processor such as a digital signal processor 10 supplies a sequence of complex numerical values A + jB where A is defined by the "n" digits al, a2...a(n) and B is defined by the "n” digits bl, b2...b(n).
- a and B of like significance such as the most significant digits al and bl, is fed to a respective one of phase modulators 11, i.e. phase modulator ⁇ l in the case of the most significant bits.
- a radio frequency (RF) carrier signal is also fed to the input of each of phase modulators 11.
- the phase modulator 11 changes the phase of the carrier signal to one of a number of predetermined output output phase levels, equispaced around a full 360°, in dependence on the state of its two control digits.
- the control digits are binary bits
- the two control bits can take on one of four states, allowing one of four 90° spaced phases to be defined.
- the example of binary digits and four-level phase modulators will be used henceforth unless otherwise stated. However, it will be understood that more levels using other than binary digits may be used.
- PA1 of power amplifiers (PA) 12 will determine whether PA1 of power amplifiers (PA) 12 is driven by phases of +/-45 0 or +/-135 0 relative to an arbitrary phase reference provided by the input radio frequency carrier signal. If PA1 has an output voltage amplitude of A 1, it therefore delivers one of the four complex signal levels:
- the combining circuit 13 combines the outputs of all power amplifiers 12, for example by voltage addition, to obtain a combined signal
- combining circuits 13 may be employed with the present invention.
- directional-coupler combining is disclosed for isolating each power amplifier from the effect of the others.
- the preferred directional coupler amplitude combining ratios are the square root of the power ratios of the power amplifiers, and the power ratios bear a declining power of two ratio to each other, such as 1 watt : 0.5 watt : 0.25 watt and so forth.
- This coupling arrangement may not deliver all the power amplifier- generated power to the load except when all power amplifiers are driven with the same phase.
- Series combining of the power amplifier outputs is preferably provided, such that the power amplifiers are not isolated from one another, but rather the combined current due to the sum of their output voltages divided by the load impedance flows in each of the power amplifiers' output circuits. If one power amplifier alters its phase and thereby alters the combined voltage and current, the current in all the power amplifiers will then change to the new value.
- This is one of the two preferred combining techniques for the present invention, and is shown in Figure 2. This technique is also illustrated in Application Serial No.
- the combining circuit 13' comprises transformers Tl, T2, T3... T(n).
- the primary of each transformer is connected to the output of its respective power amplifier 12.
- the secondaries of all transformers are connected in series and to the load. If all power amplifiers are supplied by the same DC source of voltage Vcc and generate the same saturated voltage swing (also referred to as an "amplifier power level") at their outputs, then to provide combination according to a binary weighting, the primary turns to secondary turns ratio (also referred to as a "combining ratio”) of T(i + 1) is greater than that of T(i) by a factor of two.
- Tl can have a 1 :1 primary: secondary turns ratio; then T2 has a 2:1 ratio, T3 a 4:1 ratio, etc.
- Figure 3 shows a second preferred combining circuit 13". This embodiment ensures that each power amplifier output device passes the same current waveform by assuring the same voltage one quarter wavelength away. Due to the dual-reciprocal properties of a quarter wave transmission line, ⁇ /4, if the voltage at one end is defined to be VO, then the current at the other end is determined to be V0/Z0, where Z0 is the characteristic impedance of the line.
- the transmission lines ⁇ /4 may be of the same impedance and the binary weighting may be obtained by using different Vccs in a decreasing power of two ratio. It is also possible to combine the use of output transformers as in Figure 2 with quarter- wave lines as in Figure 3, with or without scaled Vccs, as long as the Vcc for each stage divided by the transformer primary to secondary ratio and divided by the respective line impedance has a 2:1 ratio between successive stages.
- the coupling circuit combines the power amplifier outputs in power of three ratios. When ternary is used however, the power amplifiers may no longer generate constant output power, which may lead to a potential loss of efficiency.
- FIG 4 illustrates an embodiment of a phase modulator 11 of Figures 1-3. As shown, a power amplifier drive signal is formed that is controllable in phase through four 90° spaced phase values.
- a constant frequency signal referred to as the Transmit Intermediate Frequency (TXIF) signal
- TXIF Transmit Intermediate Frequency
- a phase splitter 20 generates two TXIF signals 90° apart in phase.
- a common phase splitter can be used for all pairs of IQ modulators 21, 22. Alternatively, each can have its own phase splitter.
- the balanced modulator 21 either inverts or does not invert the phase of the first split TXIF signal from the splitter 20 in dependence on the polarity of bit a(i).
- the balanced modulator 22 either inverts or does not invert the second phase split signal from the splitter 20 according to the polarity of control bit b(i).
- the balanced modulators 21, 22 preferably are Gilbert cells integrated into an integrated circuit chip, and the current outputs of Gilbert cells may be added by parallelling their outputs.
- the combined signal comprises a cosine part of sign a(i) and a sine part of sign b(i), which together define a complex signal vector having one of the four desired 90° spaced angles, which is one input to a phase comparator 25.
- a controlled oscillator 23 such as a Voltage Controlled Oscillator (VCO) generates a signal at the desired radio transmitter channel frequency and drives an associated one of power amplifiers 12.
- VCO 23 also provides an output signal to a downconvertor 24, where it is mixed with a common local oscillator frequency Fio chosen to produce a downvertor output frequency equal to TXIF.
- the TXIF output signal from the mixer 24 is then phase-compared in phase comparator 25 with the phase-modulated TXIF signal from the modulator to generate a phase error signal.
- the phase error signal from phase comparator 25 is then filtered and integrated in a loop filter 26 to provide a control signal for the VCO 23, forcing its frequency to be
- Circuits such as Figure 4 have been successfully integrated into integrated circuit chips, and within the present state of the art several such circuits can be fabricated in one chip.
- the invention can provide a single chip for implementing all phase modulators, the chip having a real control word input al, a2....a(n) and an imaginary word control input bl , b2,....b(n).
- the real word and the imaginary word are preferably changed to new values at alternate instants of a clock rather than at the same instant, so that the phase change at each clock period may only be +90° or - 90° and may never be 180°.
- This can facilitate the design of the phase comparator 25 and the loop filter 26 to effect a smooth transition of the VCO phase value from one value to the next. This may be desirable to ensure that the resultant output signal transitions smoothly between successive complex vector points to thereby preferably contain the transmitted spectral energy within an allocated channel and preferably avoid spectral spreading to adjacent channels.
- Figure 5 illustrates the formation of an instantaneous signal vector l+7j by adding the outputs of three power amplifiers having power outputs in the ratio 1 : 1/4 : 1/16 and amplitude outputs in the ratio 1 : 1/2 : 1/4.
- the power amplifier of highest power has an output amplitude of 4v2 , and can generate any one of the four vectors (4+4j), (4-4j), (-4+4j), (- -4j), which may be recognized as Quadrature Phase Shift Keying (QPSK) vectors. If the real and imaginary values change at different times, i.e. on odd and even clock cycles respectively, the vectors are Offset QPSK (OQPSK) vectors.
- OFPSK Offset QPSK
- the power amplifier of middle power likewise generates output vectors of (2+2j), (2-2j), (-2+2j) or (— 2— 2j), while the power amplifier of lowest power generates one of (1+j), (1-j), (-1+j) or (-1-j).
- any point that can be defined by three real bits and three imaginary bits can be reached. To reach points in between, additional, even lower power power amplifiers can be added to increase the number of bits used to represent the vector parts.
- the Chireix/Doherty hybrid technique of the above described Application Serial No. 09/054,063 can be used to generate a least significant remainder part that can lie anywhere within the +/-0.5 +/-0.5J circle, i.e. by combining two extra low power power amplifiers whose phases are continuously controlled and not limited to four phase values.
- phase modulator implementations may be provided.
- one modification which may be made is to replace a number of the power amplifiers of lower significant power by a pair of low power power amplifiers connected according to the hybrid Chireix/Doherty amplifier of the above incorporated Application Serial No. 09/054,063, which can implement all of the contributions of the lower significant bits by suitable control of their phases using those least significant bits. In this way, high accuracy of waveform synthesis can be achieved using a limited number of stages. All such variations are considered to lie within the scope and spirit of this invention as described by the following claims.
Abstract
Description
Claims
Priority Applications (3)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
DE19983794T DE19983794T1 (en) | 1998-12-10 | 1999-10-19 | Qam modulator for radio communication |
AU11213/00A AU1121300A (en) | 1998-12-10 | 1999-10-19 | Qam modulator for radio communications |
JP2000587506A JP2002532965A (en) | 1998-12-10 | 1999-10-19 | System and method for converting a complex stream to a modulated radio power signal |
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
US09/208,912 | 1998-12-10 | ||
US09/208,912 US6201452B1 (en) | 1998-12-10 | 1998-12-10 | Systems and methods for converting a stream of complex numbers into a modulated radio power signal |
Publications (2)
Publication Number | Publication Date |
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WO2000035160A1 true WO2000035160A1 (en) | 2000-06-15 |
WO2000035160A8 WO2000035160A8 (en) | 2001-11-08 |
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Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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PCT/US1999/024332 WO2000035160A1 (en) | 1998-12-10 | 1999-10-19 | Qam modulator for radio communications |
Country Status (7)
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US (1) | US6201452B1 (en) |
JP (1) | JP2002532965A (en) |
CN (1) | CN1154318C (en) |
AU (1) | AU1121300A (en) |
DE (1) | DE19983794T1 (en) |
MY (1) | MY130821A (en) |
WO (1) | WO2000035160A1 (en) |
Cited By (1)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2015120331A1 (en) * | 2014-02-07 | 2015-08-13 | Qualcomm Incorporated | Tri-phase digital polar modulator |
Families Citing this family (62)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US6285251B1 (en) | 1998-04-02 | 2001-09-04 | Ericsson Inc. | Amplification systems and methods using fixed and modulated power supply voltages and buck-boost control |
US6825719B1 (en) * | 2000-05-26 | 2004-11-30 | Intel Corporation | RF power amplifier and methods for improving the efficiency thereof |
FR2811826B1 (en) * | 2000-07-13 | 2002-10-11 | Centre Nat Etd Spatiales | METHOD AND CIRCUIT FOR COMPONENT DIGITAL MODULATION OF THE MODULAR OUTPUT SIGNAL THAT CAN BE NULL |
US6816016B2 (en) * | 2000-08-10 | 2004-11-09 | Tropian, Inc. | High-efficiency modulating RF amplifier |
US6472934B1 (en) * | 2000-12-29 | 2002-10-29 | Ericsson Inc. | Triple class E Doherty amplifier topology for high efficiency signal transmitters |
US6587511B2 (en) * | 2001-01-26 | 2003-07-01 | Intel Corporation | Radio frequency transmitter and methods thereof |
SE521673C2 (en) * | 2001-11-29 | 2003-11-25 | Ericsson Telefon Ab L M | Composite amplifier |
US20030125065A1 (en) * | 2001-12-27 | 2003-07-03 | Ilan Barak | Method and apparatus for generating an output signal |
US20030123566A1 (en) * | 2001-12-27 | 2003-07-03 | Jaime Hasson | Transmitter having a sigma-delta modulator with a non-uniform polar quantizer and methods thereof |
SE522479C2 (en) * | 2002-01-16 | 2004-02-10 | Ericsson Telefon Ab L M | Composite power amplifier |
US7016657B2 (en) * | 2002-01-30 | 2006-03-21 | Nokia Corporation | Apparatus, and associated method, for communication system utilizing space-generated multilevel coding |
US6924699B2 (en) * | 2003-03-06 | 2005-08-02 | M/A-Com, Inc. | Apparatus, methods and articles of manufacture for digital modification in electromagnetic signal processing |
US7545865B2 (en) * | 2002-12-03 | 2009-06-09 | M/A-Com, Inc. | Apparatus, methods and articles of manufacture for wideband signal processing |
US7245183B2 (en) * | 2002-11-14 | 2007-07-17 | M/A-Com Eurotec Bv | Apparatus, methods and articles of manufacture for processing an electromagnetic wave |
US7526260B2 (en) * | 2002-11-14 | 2009-04-28 | M/A-Com Eurotec, B.V. | Apparatus, methods and articles of manufacture for linear signal modification |
US7203262B2 (en) | 2003-05-13 | 2007-04-10 | M/A-Com, Inc. | Methods and apparatus for signal modification in a fractional-N phase locked loop system |
US7298854B2 (en) * | 2002-12-04 | 2007-11-20 | M/A-Com, Inc. | Apparatus, methods and articles of manufacture for noise reduction in electromagnetic signal processing |
US6891432B2 (en) * | 2002-11-14 | 2005-05-10 | Mia-Com, Inc. | Apparatus, methods and articles of manufacture for electromagnetic processing |
US7187231B2 (en) * | 2002-12-02 | 2007-03-06 | M/A-Com, Inc. | Apparatus, methods and articles of manufacture for multiband signal processing |
US7302011B1 (en) * | 2002-10-16 | 2007-11-27 | Rf Micro Devices, Inc. | Quadrature frequency doubling system |
US6816008B2 (en) * | 2002-12-31 | 2004-11-09 | Alion Science And Technology Corporation | Quasi-linear multi-state digital modulation through non-linear amplifier arrays |
US6859098B2 (en) | 2003-01-17 | 2005-02-22 | M/A-Com, Inc. | Apparatus, methods and articles of manufacture for control in an electromagnetic processor |
US7196578B2 (en) * | 2003-05-30 | 2007-03-27 | Lucent Technologies Inc. | Amplifier memory effect compensator |
US7336753B2 (en) * | 2003-06-26 | 2008-02-26 | Marvell International Ltd. | Transmitter |
US7091778B2 (en) * | 2003-09-19 | 2006-08-15 | M/A-Com, Inc. | Adaptive wideband digital amplifier for linearly modulated signal amplification and transmission |
US7480511B2 (en) * | 2003-09-19 | 2009-01-20 | Trimble Navigation Limited | Method and system for delivering virtual reference station data |
US7343138B2 (en) * | 2003-12-08 | 2008-03-11 | M/A-Com, Inc. | Compensating for load pull in electromagentic signal propagation using adaptive impedance matching |
US7912145B2 (en) * | 2003-12-15 | 2011-03-22 | Marvell World Trade Ltd. | Filter for a modulator and methods thereof |
US7356315B2 (en) * | 2003-12-17 | 2008-04-08 | Intel Corporation | Outphasing modulators and methods of outphasing modulation |
US7236753B2 (en) * | 2003-12-29 | 2007-06-26 | Intel Corporation | Direct outphasing modulator |
US7327803B2 (en) | 2004-10-22 | 2008-02-05 | Parkervision, Inc. | Systems and methods for vector power amplification |
US7355470B2 (en) * | 2006-04-24 | 2008-04-08 | Parkervision, Inc. | Systems and methods of RF power transmission, modulation, and amplification, including embodiments for amplifier class transitioning |
US7369819B2 (en) * | 2005-04-14 | 2008-05-06 | Harris Corporation | Digital amplitude modulation transmitter with pulse width modulating RF drive |
US8013675B2 (en) | 2007-06-19 | 2011-09-06 | Parkervision, Inc. | Combiner-less multiple input single output (MISO) amplification with blended control |
US9106316B2 (en) | 2005-10-24 | 2015-08-11 | Parkervision, Inc. | Systems and methods of RF power transmission, modulation, and amplification |
US7911272B2 (en) | 2007-06-19 | 2011-03-22 | Parkervision, Inc. | Systems and methods of RF power transmission, modulation, and amplification, including blended control embodiments |
DE602006015363D1 (en) * | 2006-04-10 | 2010-08-19 | Ericsson Telefon Ab L M | METHOD FOR COMPENSATING SIGNAL DISTORTIONS IN COMPOSITE AMPLIFIERS |
US7937106B2 (en) * | 2006-04-24 | 2011-05-03 | ParkerVision, Inc, | Systems and methods of RF power transmission, modulation, and amplification, including architectural embodiments of same |
US8031804B2 (en) | 2006-04-24 | 2011-10-04 | Parkervision, Inc. | Systems and methods of RF tower transmission, modulation, and amplification, including embodiments for compensating for waveform distortion |
US20070286308A1 (en) * | 2006-06-12 | 2007-12-13 | Thomas Holtzman Williams | System and method for modulated signal generation method using two equal, constant-amplitude, adjustable-phase carrier waves |
US7881401B2 (en) * | 2006-11-17 | 2011-02-01 | Infineon Technologies Ag | Transmitter arrangement and signal processing method |
US7620129B2 (en) * | 2007-01-16 | 2009-11-17 | Parkervision, Inc. | RF power transmission, modulation, and amplification, including embodiments for generating vector modulation control signals |
EP1962438A1 (en) * | 2007-02-22 | 2008-08-27 | Sony Deutschland GmbH | Method of transmitting data and modem |
CN101262458B (en) * | 2007-03-06 | 2011-08-17 | 北京朗波芯微技术有限公司 | Method for modulating digital signal to RF signals and digital RF converter |
WO2008144017A1 (en) * | 2007-05-18 | 2008-11-27 | Parkervision, Inc. | Systems and methods of rf power transmission, modulation, and amplification |
WO2009005768A1 (en) | 2007-06-28 | 2009-01-08 | Parkervision, Inc. | Systems and methods of rf power transmission, modulation, and amplification |
US8098726B2 (en) * | 2007-07-27 | 2012-01-17 | Intel Corporation | Subranging for a pulse position and pulse width modulation based transmitter |
US20090036064A1 (en) * | 2007-07-31 | 2009-02-05 | Ashoke Ravi | Digital integrated transmitter based on four-path phase modulation |
US7773669B2 (en) * | 2007-08-10 | 2010-08-10 | Intel Corporation | Cascaded phase pulse position and pulse width modulation based digital transmitter |
WO2009113000A2 (en) * | 2008-03-10 | 2009-09-17 | Nxp B.V. | Output stage for a digital rf transmitter, method for providing an rf output signal in a digital rf transmitter, and digital rf transmitter |
US8472896B2 (en) * | 2010-09-10 | 2013-06-25 | Intel Corporation | Method and apparatus for transformer power combiner and dynamic power control for outphasing power amplifiers |
KR20140026458A (en) | 2011-04-08 | 2014-03-05 | 파커비전, 인크. | Systems and methods of rf power transmission, modulation, and amplification |
EP2715867A4 (en) | 2011-06-02 | 2014-12-17 | Parkervision Inc | Antenna control |
WO2013015778A1 (en) * | 2011-07-25 | 2013-01-31 | Andrew Llc | Actively tuned circuit having parallel carrier and peaking paths |
CN104620510A (en) * | 2012-09-14 | 2015-05-13 | 日本电气株式会社 | Transmitter |
US20150080063A1 (en) | 2013-09-17 | 2015-03-19 | Parkervision, Inc. | Method, apparatus and system for rendering an information bearing function of time |
JP6481618B2 (en) * | 2013-12-19 | 2019-03-13 | 日本電気株式会社 | Transmitting apparatus and transmitting method |
US9608305B2 (en) * | 2014-01-14 | 2017-03-28 | Infineon Technologies Ag | System and method for a directional coupler with a combining circuit |
JP2016119609A (en) | 2014-12-22 | 2016-06-30 | 富士通株式会社 | Amplification device |
US9979404B1 (en) * | 2016-12-30 | 2018-05-22 | Silicon Laboratories Inc. | Multi-phase amplitude and phase modulation |
US10044383B2 (en) * | 2016-12-30 | 2018-08-07 | Silicon Laboratories Inc. | Sinewave generation from multi-phase signals |
CN109918047A (en) * | 2019-02-01 | 2019-06-21 | 深圳市南方硅谷微电子有限公司 | Plural modulus method and apparatus based on modem |
Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4433312A (en) * | 1981-12-18 | 1984-02-21 | Kahn Leonard R | Method and means for modulating waves |
US4580111A (en) * | 1981-12-24 | 1986-04-01 | Harris Corporation | Amplitude modulation using digitally selected carrier amplifiers |
US5612651A (en) * | 1996-01-02 | 1997-03-18 | Loral Aerospace Corp. | Modulating array QAM transmitter |
WO1997048219A2 (en) * | 1996-06-12 | 1997-12-18 | Ericsson Inc. | Transmitter for qam encoded data |
WO1999052206A1 (en) * | 1998-04-02 | 1999-10-14 | Ericsson, Inc. | Hybrid chireix/doherty amplifiers power waveform synthesis |
Family Cites Families (41)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US2210028A (en) | 1936-04-01 | 1940-08-06 | Bell Telephone Labor Inc | Amplifier |
US3448366A (en) | 1966-11-28 | 1969-06-03 | Mallory & Co Inc P R | Multiphase static inverter |
US3777275A (en) | 1972-01-31 | 1973-12-04 | Bell Telephone Labor Inc | Linear amplification with nonlinear devices |
US3805139A (en) | 1972-09-29 | 1974-04-16 | Ibm | Programmed waveform power inverter control system |
US3909742A (en) | 1974-08-19 | 1975-09-30 | Bell Telephone Labor Inc | Linear amplification using nonlinear devices and feedback |
US3906401A (en) | 1974-09-03 | 1975-09-16 | Bell Telephone Labor Inc | Feedforward error correction in interferometer modulators |
US3927379A (en) | 1975-01-08 | 1975-12-16 | Bell Telephone Labor Inc | Linear amplification using nonlinear devices and inverse sine phase modulation |
US4090147A (en) | 1977-07-20 | 1978-05-16 | Bell Telephone Laboratories, Incorporated | Interferometric amplifier |
US4178557A (en) | 1978-12-15 | 1979-12-11 | Bell Telephone Laboratories, Incorporated | Linear amplification with nonlinear devices |
US4315107A (en) | 1979-10-15 | 1982-02-09 | Bell Telephone Laboratories, Incorporated | Telephone range extender with gain |
NL8001903A (en) | 1980-04-01 | 1981-11-02 | Philips Nv | DEVICE FOR AMPLIFYING A MODULATED CARRIER SIGNAL. |
NL8101109A (en) | 1981-03-09 | 1982-10-01 | Philips Nv | ELECTRONIC DEVICE FOR GENERATING AN AMPLITUDE AND PHASE MODULATED CARRIER SIGNAL. |
US4509017A (en) | 1981-09-28 | 1985-04-02 | E-Systems, Inc. | Method and apparatus for pulse angle modulation |
US4791815A (en) | 1986-04-11 | 1988-12-20 | Matsushita Electric Industrial Co., Ltd. | Cyclically driven gyro and adjusting system therefor |
US4862116A (en) | 1988-10-17 | 1989-08-29 | The United States Of America As Represented By The Secretary Of The Navy | Active phase and amplitude modulator |
JPH0379575A (en) | 1989-08-23 | 1991-04-04 | Mitsubishi Electric Corp | Mutual communication device for elevator in emergency |
JPH0495409A (en) | 1990-08-13 | 1992-03-27 | Fujitsu Ltd | Amplifier |
US5077539A (en) | 1990-12-26 | 1991-12-31 | Apogee Technology, Inc. | Switching amplifier |
US5767750A (en) | 1992-03-30 | 1998-06-16 | Kabushiki Kaisha Toshiba | Modulator |
GB9209982D0 (en) | 1992-05-08 | 1992-06-24 | British Tech Group | Method and apparatus for amplifying modulating and demodulating |
SE470455B (en) | 1992-08-24 | 1994-04-11 | Ericsson Telefon Ab L M | Device for compensating the phase rotation in the feedback loop of a Cartesian feedback power amplifier |
JPH07115728A (en) | 1992-08-28 | 1995-05-02 | Tai-Her Yang | Circuit for outputting multi-stage composite voltage by a plurality of independent dc power supplies |
EP0598585B1 (en) | 1992-11-16 | 1999-03-31 | Linear Modulation Technology Ltd | Automatic calibration of the quadrature balance within a cartesian amplifier |
FR2705844B1 (en) | 1993-05-28 | 1995-07-21 | Thomson Csf | Method and device for amplitude modulation of a radiofrequency signal. |
US5420541A (en) | 1993-06-04 | 1995-05-30 | Raytheon Company | Microwave doherty amplifier |
US5559468A (en) | 1993-06-28 | 1996-09-24 | Motorola, Inc. | Feedback loop closure in a linear transmitter |
DE4420376C2 (en) | 1993-09-22 | 1998-09-17 | Hewlett Packard Co | Quadrature modulator |
US5365187A (en) | 1993-10-29 | 1994-11-15 | Hewlett-Packard Company | Power amplifier utilizing the vector addition of two constant envelope carriers |
FR2712126B1 (en) | 1993-11-05 | 1995-12-01 | Thomson Csf | Power amplifier of the H-bridge type and its blocking means and power amplifier device comprising such amplifiers. |
US5563780A (en) | 1993-12-08 | 1996-10-08 | International Power Systems, Inc. | Power conversion array applying small sequentially switched converters in parallel |
US5574967A (en) | 1994-01-11 | 1996-11-12 | Ericsson Ge Mobile Communications, Inc. | Waste energy control and management in power amplifiers |
US5778028A (en) | 1994-06-13 | 1998-07-07 | Zenith Electronics Corporation | DC removal circuit for digital signal |
US5438301A (en) | 1994-07-25 | 1995-08-01 | At&T Corp. | Modem having a phase corrector and a voltage controlled oscillator implemented using a multi-stage ring oscillator |
DE19535075A1 (en) | 1994-10-21 | 1996-04-25 | Deutsche Telekom Ag | Quadrature amplitude modulation transmission system |
JP2885660B2 (en) | 1995-01-31 | 1999-04-26 | 日本無線株式会社 | Amplitude modulation circuit |
US5732333A (en) | 1996-02-14 | 1998-03-24 | Glenayre Electronics, Inc. | Linear transmitter using predistortion |
US5734565A (en) | 1996-08-16 | 1998-03-31 | American Superconductor Corporation | Reducing switching losses in series connected bridge inverters and amplifiers |
US5900778A (en) | 1997-05-08 | 1999-05-04 | Stonick; John T. | Adaptive parametric signal predistorter for compensation of time varying linear and nonlinear amplifier distortion |
US5930128A (en) | 1998-04-02 | 1999-07-27 | Ericsson Inc. | Power waveform synthesis using bilateral devices |
US6023885A (en) | 1998-04-27 | 2000-02-15 | Southpac Trust International, Inc. | Floral sleeve having a decorative pattern |
US5990734A (en) | 1998-06-19 | 1999-11-23 | Datum Telegraphic Inc. | System and methods for stimulating and training a power amplifier during non-transmission events |
-
1998
- 1998-12-10 US US09/208,912 patent/US6201452B1/en not_active Expired - Lifetime
-
1999
- 1999-10-19 AU AU11213/00A patent/AU1121300A/en not_active Abandoned
- 1999-10-19 JP JP2000587506A patent/JP2002532965A/en not_active Withdrawn
- 1999-10-19 WO PCT/US1999/024332 patent/WO2000035160A1/en active Application Filing
- 1999-10-19 CN CNB998143588A patent/CN1154318C/en not_active Expired - Fee Related
- 1999-10-19 DE DE19983794T patent/DE19983794T1/en not_active Withdrawn
- 1999-11-15 MY MYPI99004961A patent/MY130821A/en unknown
Patent Citations (5)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US4433312A (en) * | 1981-12-18 | 1984-02-21 | Kahn Leonard R | Method and means for modulating waves |
US4580111A (en) * | 1981-12-24 | 1986-04-01 | Harris Corporation | Amplitude modulation using digitally selected carrier amplifiers |
US5612651A (en) * | 1996-01-02 | 1997-03-18 | Loral Aerospace Corp. | Modulating array QAM transmitter |
WO1997048219A2 (en) * | 1996-06-12 | 1997-12-18 | Ericsson Inc. | Transmitter for qam encoded data |
WO1999052206A1 (en) * | 1998-04-02 | 1999-10-14 | Ericsson, Inc. | Hybrid chireix/doherty amplifiers power waveform synthesis |
Non-Patent Citations (1)
Title |
---|
MORAIS D H ET AL: "NLA-QAM: A METHOD FOR GENERATING HIGH-POWER QAM SIGNALS THROUGH NONLINEAR AMPLIFICATION", IEEE TRANSACTIONS ON COMMUNICATIONS, vol. 30, no. 3, 1 March 1982 (1982-03-01), New York, USA, pages 517 - 522, XP002067429, ISSN: 0090-6778 * |
Cited By (2)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
WO2015120331A1 (en) * | 2014-02-07 | 2015-08-13 | Qualcomm Incorporated | Tri-phase digital polar modulator |
US9344038B2 (en) | 2014-02-07 | 2016-05-17 | Qualcomm Incorporated | Tri-phase digital polar modulator |
Also Published As
Publication number | Publication date |
---|---|
DE19983794T1 (en) | 2002-01-24 |
WO2000035160A8 (en) | 2001-11-08 |
MY130821A (en) | 2007-07-31 |
US6201452B1 (en) | 2001-03-13 |
CN1154318C (en) | 2004-06-16 |
JP2002532965A (en) | 2002-10-02 |
CN1375150A (en) | 2002-10-16 |
AU1121300A (en) | 2000-06-26 |
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