WO2003073117A1

WO2003073117A1 - Sub-picotesla magnetic field detector

Info

Publication number: WO2003073117A1
Application number: PCT/US2003/005752
Authority: WO
Inventors: Nilesh Tralshawala; Alexander Bakharev; Yuri Polyakov
Original assignee: Cardiomag Imaging, Inc.
Priority date: 2002-02-26
Filing date: 2003-02-26
Publication date: 2003-09-04
Also published as: US20040239319A1; ATE522820T1; EP1478935A1; CN101303398B; CN101303398A; EP1478935A4; CN1639582A; EP1478935B1; US7365534B2; AU2003230570A1

Abstract

An instrument for measuring sub-pico Tesla magnetic fields using a superconducting quantum interference device (SQUID) inductively coupled to an unshielded gradiometer includes a filter for filtering magnetically- and electrically coupled radio frequency interference (RFI) away from the SQUID. This RFI is principally coupled to the SQUID via the unshielded gradiometer. In addition, a shielding enclosure is used to electromagnetically shield the filter circuit from the SQUID, and a method is employed to increase the impedance between the input coil and the SQUID without diminishing the overall sensitivity of the instrument.

Description

SUB-PICOTESLA MAGNETIC FIELD DETECTOR

BACKGROUND OF THE INVENTION

Cross-Reference To Related Application

The present application claims priority from U.S. Serial No. 60/360,090, filed on February 26, 2002, filed by at least one inventor common to the present application, and is hereby incorporated by reference.

Field of the Invention

The present invention relates generally to the field of measuring magnetic fields. More specifically, the present invention relates to measuring low-level magnetic fields with gradiometers and magnetometers using superconducting quantum interference devices (SQUIDs) in unshielded environments.

Discussion of the Prior Art

A superconducting quantum interference device (SQUID) magnetic sensor is at the heart of many sensitive magnetometers aimed at measuring magnetic fields below about 10 Tesla (T). This level is within the range, for example, of magnetic fields produced by living organisms (often referred to as biomagnetic fields).

SQUIDs are sensitive to magnetic flux Φ_B. Magnetic flux Φ_B may be defined as the projection of the average magnetic field threading a given area along a vector z positioned normally to the area, or mathematically:

Φ_B = B₂*A (1)

A low-Tesla direct current (DC) SQUID typically consists of two nominally identical Josephson junctions serially connected in a superconducting, electrically continuous loop, typically on the order of 10^"4 to 10^"2 millimeters (mm) in diameter. SQUTD-based magnetometers and gradiometers are among the most sensitive magnetic field detectors in current use.

SQUIDs are typically produced on chips, using Niobium-Aluminum-Aluminum Oxide-Niobium (Nb-Al-AlO_x-Nb) junction technology, with associated junctions and the SQUID loop formed from thin films. The micron-scale features of the device may be formed using photolithographic techniques. The SQUID chip is typically enclosed in a superconducting shield for screening the device from ambient magnetic flux. The magnetic flux to be measured is typically intercepted by considerably larger diameter loops or coils (for example, 10 - 20 mm) inductively coupled to the SQUID via an input coil. These larger coils are usually made of thin insulated superconducting wire (for example, Nb) wound over an insulating cylindrical support. A device having a single coil or loop may be referred to as a magnetometer, a device having combinations of more than one coil or loop may be referred to as a gradiometer. Such a device is schematically illustrated, for example, in Figure 4.

Unfortunately, this unprecedented sensitivity of SQUID-based gradiometers comes at a price, as sensitivity can cause the device to become overwhelmed by ambient noise and to stop working when exposed to radio frequency interference (RFI). As a result, these devices can often only be operated in heavily shielded enclosures, which may be impractical for all real life applications. Accordingly, it would be quite beneficial if SQUID-based devices could be operated without such shielding. If we can do this then we have a practical sensitive magnetic field measuring instrument. The present application discloses a method and apparatus for achieving this goal.

In the presence of RFI, a SQUID may lose sensitivity or even cease to function. Sources of strong RFI include, for example, ultrasound machines in hospitals, AM and FM radio signals, TV and cellular communications transmissions. At frequencies lower than the RF band, SQUID electronics can be used to measure the noise, and known software techniques can be used to eliminate this noise (e.g., Bick et al., "SQUID Gradiometry for Magnetocardiography Using Different Noise Cancellation Techniques").

A simple but often impractical solution to RFI elimination in prior art systems has been to surround the system with a few layers of fine copper mesh and isolate the area of operation. The copper mesh reduces RFI considerably, but doesn't eliminate it, as it is difficult to cut down transmission through connecting cables. While the SQUTD itself may be suitably shielded inside a small Nb tube, an unshielded gradiometer that picks up the measurement signal and feeds it to the SQUID will nonetheless couple RFI into the SQUID, as the gradiometer itself cannot be shielded (otherwise it cannot pick up the signal to be measured). Thus, there is a need for a technique that allows the gradiometer to couple the signal of interest into the SQUID, without additionally coupling the RFI into the SQUTD.

The following references provide for a general description of prior art SQUTD systems, but they fail to provide effective means for shielding the SQUID from radio frequency interference.

The Japanese patent to Fujimaki (JP 4212079) provides for a SQUID magnetic field sensor, wherein damping resistors Rl and R2 are used to eliminate only the magnetic part of the RFI.

The non-patent literature to Ishikawa et al. entitled, "Effect of RF Interference on Characteristics of a DC SQUID System", and Koch et al (Appl. Phys. Lett., vol 65, pp. 100-102) entitled, "Effects of radio frequency radiation on the dc SQUID," provide background information related to RFI interference in SQUID systems.

The non-patent literature to Bick et al. ("SQUTD Gradiometry for Magnetocardiography Using Different Noise Cancellation Techniques"), and Tarasov et al. ("Optimization of Input Impedance and Mechanism of Noise Suppression in a DC SQUID RF Amplifier") illustrate, in general, the use of noise cancellation techniques with a SQUTD device.

The U.S. patent to Simmonds (5,319,307) covers improving SQUTD performance. References to a superconducting shielding layer are directed to shielding the SQUID chip from RFI, and it should be noted that in general all SQUIDs, even those used in shielded enclosures, are kept inside a superconducting Nb tube with gradiometers connected from the outside through small holes in the Nb tube.

The U.S. patent to Colclough (5,532,592,) covers electronics (flux-locked loops) in multichannel systems. It should be noted that the reference to a brass enclosure is a routine procedure in electronics to shield against RFI; but this procedure is inadequate against RFI transmitted through a wire that goes through enclosures.

The U.S. patent to Seppa (6,066,948) discloses damping individual junctions of a SQUTD. It should be noted that this is a common procedure and more information regarding this procedure can be found in the book by Weinstock entitled, "Applications of Superconductivity" (Kluwer, Netherlands, 2000). It should further be noted that this procedure allows for the damping of internal oscillations of junctions that affect operation of the SQUIDs and does not reduce RFI coupled to the SQUID itself.

The U.S. patent to Steinbach et al. (6,169,397) describes a method for damping internal resonances of the SQUTD. The damping helps shield the SQUTD from magnetic part of the RFI and is similar to the Japanese patent by Goto (JP 4160380) that provides for a general background in noise suppression techniques as implemented in prior art SQUTD systems.

Furthermore, the Japanese patent to Kawai (JP 7198815) appears to teach along the same lines as that of the Steinbach et al. patent.

SUMMARY OF THE INVENTION

The present invention provides an apparatus and method for preventing RFI from coupling into a SQUTD without compromising the signal to noise ratio of the system, and while operating the system in unshielded real life situations.

In the preferred embodiment, filter circuits are incorporated in a novel manner to remove RFI from the SQUTD without shielding gradiometer loops. The filter circuits are formed using a combination of resistors and capacitors (RC circuits), where the resistors shunt magnetically-coupled RFI from an input coil of the SQUTD, and the capacitors shunt electrically-coupled RFI from the SQUTD. It should be noted that even though a variety of RC circuits employing conventional resistors and capacitors are described, any form of filter circuit that has similar properties (for example, with respect to cut-off frequency and sharpness) can be used. For example, a filter made up of superconducting striplines that cuts out components of RFI from getting coupled into the shielded SQUTD from unshielded gradiometers may be effectively used.

The present invention also contemplates an enclosure for electromagnetically isolating the filter circuit from the SQUTD for improved RFI shielding, and a method for improved RFI decoupling from the SQUTD that enables an impedance ZQ between the input coil and the SQUTD to be increased without a loss of sensitivity in the apparatus.

This invention allows for widespread usage of SQUTD systems in unshielded environments, even in the presence of strong RFI. This opens up the possibility of employing SQUIDs in various biomedical and nondestructive evaluation applications without sacrificing performance. In effect, the invention enables manufacture of a practical sub-picotesla detector.

BRIEF DESCRIPTION OF THE DRAWINGS

A more complete understanding of the invention may be obtained by reading the following description of specific illustrative embodiments of the invention in conjunction with the appended drawing in which:

Figure 1 illustrates a schematic of symmetric SQUTD bias electronics, wherein the twisted wire pairs (twisting is not shown) prevent flux from threading the loop;

Figure 2 illustrates a schematic of symmetric SQUTD heater electronics, wherein the twisted wire pairs (twisting is not shown) prevent flux from threading the loop;

Figure 3 illustrates a schematic of a feedback/modulation coil as coupled to a SQUTD;

Figure 4 illustrates a first embodiment of the present invention;

Figure 5 illustrates a second embodiment of the present invention;

Figure 6 illustrates an equivalent circuit diagram for the embodiment of Figure 4 in low frequency instances;

Figure 7 illustrates an equivalent circuit diagram for the embodiment of Figure 4 in high frequency instances;

Figure 8 illustrates a first variation of the embodiment of Figure 4;

Figure 9 illustrates a first variation of the embodiment of Figure 5;

Figure 10 illustrates a second variation of the embodiment of Figure 4;

Figures 11(a) - 11(d) illustrate a SQUTD design according to principles of the present invention that enables reduction of RFI coupling into the SQUTD. A conventional design is shown in Figures 11(a) and 11(c), and the inventive design is shown in Figures 11(b) and 11(d)); and

Figure 12 illustrates a niobium shield designed for holding the SQUTD in a chamber which is electromagnetically isolated from the filter circuits of Figures 4 - 10. In the various figures, like reference numerals designate like or similar elements of the invention.

DESCRIPTION OF THE PREFERRED EMBODIMENTS

The present disclosure is to be considered as an exemplification of the principles of the invention and the associated functional specifications for its construction, and is not intended to imply limitations to the invention beyond those that are specifically claimed. Those skilled in the art may envision other possible variations beyond those exemplified here that fall within the scope of the present invention as claimed.

Figure 4 presents a circuit diagram for a SQUID-based gradiometer constructed according to a first embodiment of the present invention. Conventionally, apparatus 100 includes a gradiometer 10 (represented in Figure 4 by inductance L_g) coupled to a SQUTD 20 (with washer inductance L_SQ) via an input coil 30 (represented by inductance L, and having a mutual inductance M, and capacitance C, with respect to the SQUTD washer 20).

RFI may be coupled into SQUTD 20, in two ways: electrically and magnetically. For example, with reference to Figure 4, RFI may couple into the SQUID washer 20 by means of connecting wires (such as transmission lines 14, 14a coupling gradiometer 10 via the input coil and/or connecting wires 45 coupling amplifier 50 via transformer 40 and/or, with reference to Figure 3, transmission lines 15 coupling RFI via the feedback/modulation coil 33) acting like electromagnetic antennae. RFI can also be coupled into the SQUID washer 20 via magnetic flux threading various loops formed by the transmission lines 14, 14a and 45. In addition, under some circumstances, RFI may produce a large DC field on the SQUTD washer 20. Since SQUIDs are very low impedance devices, they are generally most affected by magnetically-coupled RFI. Electrically-coupled RFI may however also be substantial, especially near and above FM radio band frequencies, at which point SQUTD connecting wires can function as transmission lines.

Fundamentally, RFI and other forms of electromagnetic interference (EMI) may get coupled into a SQUTD via any electronic connections. As has been understood, RFI may be reduced or eliminated by employing symmetric electronics that allow one to remove a ground connection to SQUTD. The symmetry of the electronics enables transmitted RF energy that is coupled into the SQUTD to be reduced. For example, with reference to Figure 3, RFI picked up through transmission line 15, including residual energy that may be coupled through the feedback/modulation coil 33 and the rest of the electrical connections to SQUTD washer 20, may be eliminated in accordance with the principles of the present invention by using special symmetric filter circuits.

Symmetric SQUTD electronics eliminate ground loop issues. Figures 1 and 2 show the symmetric SQUTD bias and heater electronics, respectively. In Figure 2, heating occurs in resistor 7 (depicted as R_H). Symmetry ensures that if connecting wires act as antennae, RFI voltages induced on them may be canceled out at the location of the SQUTD.

As illustrated for example by Figures 1 - 3, symmetric signal sources 1, 2 and 3 place signals onto transmission lines 17, 16 and 15. While doing so, RFI and other ambient noise also gets transmitted via the wires 15-17. This induces RF electric fields on transmission lines 15-17, and magnetic flux Φ and magnetically-coupled interference RFφ in the loops formed by these transmission lines 15-17.

As illustrated in figures 1 and 3, symmetrical RC filters 5 (f_c ~ 1-10 megahertz) and capacitors 6 prevent standing waves from being set up at resonant frequencies: (a) on transmission lines 15 - 17 and 45 at near 10- 100s of megahertz, and (b) between SQUTD washer 20 and either the input coil 30 and/or the feedback/modulation coil 33 at a few gigahertz. Additionally, if transmission lines 15 - 17 and 45 are configured as tightly twisted wire pairs, virtually no magnetic flux Φ threads the associated circuit loops. Circuit symmetry ensures, for example, that if the transmission lines 17 of Figure 1 act as antennae, the RFI voltage induced on them cancels out at the SQUTD washer 20.

Figure 3 illustrates feedback/modulation coil 33, which shares SQUTD feedback and modulation circuitry. Magnetic interference through the loop is eliminated by tightly twisted wire pairs forming transmission lines 15 (so that Φ is effectively 0). It should be noted that an antenna-like pick up of RFI can still be coupled to the SQUTD through capacitive coupling between the feedback coil 33 and the SQUTD washer 20. Capacitance Cf of the modulation coil 33 may typically be about 10 picofarads (pF). The modulation signal has components up to 1 megahertz (MHz). Thus, an RC filter 5 is chosen such that it has an effective bandwidth greater than 10 MHz, and a capacitance C large enough (compared to C_f) to short most of the RFI from the SQUTD washer 20. Representative values for RC filter 5 are R =100 ohms (Ω) and C = 1 nanofarads (nF).

Figure 4 illustrates a first embodiment of the present invention as a component of measuring apparatus 100. RC filter 5 (also illustrated in Figure 3) can be used to cut down the antenna-coupled RFI, but gradiometer 10 also introduces magnetic flux threading loop formed by transmission lines 14. As a result, to eliminate both the antenna coupled RFI and magnetic flux RFφ, the invention of Figure 4 couples resistive shunts 60 to grounding capacitor 70 in order to short out this magnetic flux from component loop 14a and input coil 30. Alternatively, a single resistive shunt 60 may be coupled with symmetrical RC filters 5 as shown for measuring apparatus 200 in Figure 5.

In order to better understand how the present invention works, parameters suitable for a working system are illustrated below. It should be noted that these specific examples are provided for illustrative and descriptive purposes only, and therefore should not be inferred to limit the scope of the invention as claimed.

The impedance values at various operating frequencies are tabulated in Table 1 for the circuit 100 of Figure 4. The values of various parameters are: Ci =140 pF (measured), Li = 300 nanohenries (nH), Cg = 10000 nF, R_s = 1.5 Ω.

Table 1. Impedance calculations for embodiment in Figure 4.

Impedance values for the circuit 200 of Figure 5 are provided in Figure 2. All values are the same as in table 1, except Rs = 3 'Ω and RQ = 1.5 Ω. The circuit 200 of Figure 5 is therefore essentially equivalent to the circuit 100 of Figure 4.

Table 2. Impedance calculations for embodiment in Figure 5.

For lower frequencies (i.e., below 5 MHz), the input coil impedance Z_Ll is low enough and the wavelength of accompanying RFI is long enough for the circuit 100 of Figure 4 to be represented as the equivalent circuit 300 of Figure 6. As may be observed from Tables 1 and 2 and Figures 4 and 5, the grounding tap capacitor 70 (represented as Cg) is able to effectively shunt out the electrical component of RFI pickup from the SQUTD because the capacitive impedance Zc, between the input coil 30 and the SQUTD washer 20 is much greater than Zc_g+ Rs (or Zc_g+R_g of Table 2).

At higher frequencies, the circuit 100 of Figure 4 behaves in accordance with the equivalent circuit 400 shown in Figure 7 with distributed L-C circuit elements: the distributed input coil elements 30 and distributed inductive SQUTD washer elements 20, coupled via distributed capacitive impedance 21 and mutual inductance 22. Representative approximations for elements dZα, dZ in this case are tabulated in the last two columns of Tables 1 and 2. These approximations are estimated by considering that once the partial inductive impedance of a certain length of the feedback coil 30 (where dZu is proportional to the length of input coil 30) starts to become larger than the capacitive impedance 21 between the feedback coil 30 and the SQUTD washer 20 (where dZc, is inversely proportional to the length of input coil 30, because the coil width is fixed for both L and C) over the same length segment, then it can effectively be considered to behave as a distributed LC network. This may occur, for example, with values of about 10-20 Ω for ZLi and Z_Cl. These numbers are still larger than Z_Cg+ Rs (or Zcg+Rg for Table 2) at those frequencies by a factor of approximately 10, so that shunting by RC circuit 60, 70 is still effective. At frequencies in excess of 1 GHz, the system 30-21-22-20 of Figure 7 behaves as a transverse magnetic (TM) mode resonator coupled to a well-damped (with Rs or Rg) input loop circuit, thus still avoiding instability of operation.

As illustrated for example by Figure 4, the shunt resistors 60 effectively remove the RF magnetic flux threading the input loop defined by transmission line 14a from affecting the SQUTD by shorting the gradiometer loop defined by transmission line 14. Z_L, is much greater than Rs for frequencies higher than about 5 MHz (for example, as shown in Tables 1 and 2). For lower frequencies, shunting resistors Rs still help by shunting part of the RF flux away from SQUTD washer 20. In principle, this effect may be further improved by reducing the value of the Rs- Unfortunately, there is a trade-off between smaller R_s and the flux noise it adds into the SQUID (from Johnson current noise coupled through the input coil 30 according to the following relationship:

= (i_K) = j4k 7R *> fa) = M,(i.) &

where kβ is the Boltzmann constant and T is the temperature of the resistor R, i_n is the Johnson current noise and Φ_n is the flux noise induced in the SQUID.

Therefore, we can conclude that for the apparatuses 100, 200 of Figures 4 and 5, the optimum value for Rs is 3 Ω (2* Rs in Table 1 or Rs in Table 2). It should, however, be noted that this optimum value may vary based upon other parameters associated with the circuitry of the system of the present invention.

In light of the preceding discussion, it is clear that it could prove very difficult to eliminate magnetically coupled low frequency RFI (below 5 MHz). In this case, we would like to point out that we could be better served by using a conventional SQUTD flux-locked loop (FLL) at 5 MHz or higher (for example, see the book by H. Weinstock entitled, "Applications of Superconductivity," Kluwer, Netherlands, 2000). In this case, the troublesome low frequency RFI can be nulled by the FLL as it would now be fast enough to track the RFI in this frequency range. Another advantage that will be gained from increasing FLL frequency is that the slew rate will also be faster, and thus more immune to fast switching noise from nearby major power sources and electric lightening in the atmosphere.

Additional variations on the inventive embodiments of Figures 4, 5 include featuring a shunt capacitors 71 (represented by Cs) in series with the shunt resistors 60 (see, e.g.,circuits 500 and 600 of Figures 8 and 9), and featuring an additional shunt resistor 61 (represented by R) in parallel with the circuit defined by shunt resistors 60 and grounding capacitor 70(see, e.g.,circuit 700 of Figure 10). The shunt capacitor 71 is chosen such that it forms a high pass circuit (with Rs and L,) that blocks low frequency flux noise RFφ from getting to the SQUTD washer 20. Introduction of Cs however may, in some cases, cause instability of SQUTD operation. This problem can be avoided by circuit 700 of Figure 10, where parallel circuit shunt resistor 61 can be made to have a very small resistance. This helps to reduce RFI at frequencies lower than 5 MHz.

The embodiments illustrated in Figures 4 and 10 are simple and compact, and thereby more resistant to parasitic effects than the embodiments illustrated in Figures 5, 8 and 9. On the other hand, the embodiment illustrated in Figure 5 has the advantage that R_g can be made much smaller, thus making Zc_g+R_g much smaller than Zo This approach will improve the RF voltage filtering without introducing additional flux noise into the SQUTD because of the symmetry of the circuit 200. Also, as illustrated by the circuit 600 in Figure 9, Rs can be lowered independently for filtering RF magnetic pickup, and only one additional shunt capacitor 71 needs to be added. In the circuit 500 of Figure 8, R_s can be reduced, thus making Zc_g+Rs much smaller than Zc, and thereby enabling RF voltage filtering to improve. But, in this case, two additional shunt capacitors 71 are required.

While only a few specific resistive and capacitive filters are illustrated in the present description, one skilled in the art will readily recognize that any other form of filter circuit that has similar properties (cut-off frequency and sharpness of characteristics and elimination of both the electric and magnetic components of the interference) may be used. As an example, one embodiment could include a superconducting filter made up of superconducting striplines that cuts out all components of RFI from getting coupled into the shielded SQUTD from unshielded gradiometers.

Tables 1 and 2 suggest that if the SQUTD is redesigned such that the capacitance between the input coil 30 and the SQUTD washer 20 (represented by C,) is reduced, then Zc, will become larger. This increased impedance makes the SQUTD 20 more immune to electrical components of RFI.

Figures 11(a) - 11(d) shows a SQUTD including SQUTD washer 20 and spiral input coils 30, 31. Coils 30, 31 are separated from the SQUID washer 20 by an insulator

29 providing a separation of thickness t. Only N=5 turns of the input coils 30, 31 are shown for clarity, but in practical designs N may approach 100 (for a detailed discussion, including inductance calculations and formulae that follow, please refer to

Chapters 1 and 2 in the book by H. Weinstock entitled, "Applications of

Superconductivity" Kluwer, Netherlands, 2000). Figures 11(c) and 11(d) show a top view of the SQUTD, and Figures 11(a) and 11(b) show a cross-sectional view taken through the dashed line "e-e". Reducing the line width, w, of the input coil 31 as w compared to input coil 30 will decrease the capacitance in that proportion as C ∞ N - —

(compare Figure l ie with l id).

The mutual inductance between the input coil 30, 31 and the SQUTD washer 20, Mi, is given by:

(3) M, * N - L_SQ

where L_SQ is the inductance of the SQUID washer. Accordingly, Mi is unchanged by reduction in line width w. The input coil inductance, Li, is given by:

N ' L_SQ + L (4) strip

where L_stπp is the stripline inductance of the lines that make up the input coil 30.

Although, Z, « μ₀ increases as w is decreased, for sufficiently large N (for w + 2t nominal SQUTD design this corresponds to N greater than 20), L_stnp can be ignored and L_t ~ TV^{2 •} L_SQ . Here μo is the permittivity of the free space. Thus, for practical designs, Li is also independent of w. Thus, in summary, the reduction in line width of the input coil lines (as illustrated by input coil 30 and input coil 31 in Figures 11(c) and 11(d)) results in a decrease in C„ but as Mi and Li are unchanged, does not lead to any loss of sensitivity

S oc — '^■ (here L_g is the gradiometer inductance and is independent of the SQUID

L, + L_g design). The decrease in C, leads to increase in Zc, making it that much larger than Zc_g, and this in turn further reduces the electrical RFI into the SQUTD washer 20 (please refer to Tables 1 and 2 and Figures 6 and 7).

RF currents flowing through the filter circuit wires could also get coupled into the SQUTD if the filter wires are close to the SQUID washer 20. To prevent this (see, e.g., Figures 12(a) - 12(c)), a SQUTD shield 90 including two electromagnetically isolated chambers 91, 92 may be used to separately house the SQUTD 91a (shown in chamber 91) and the filter circuits 92a (shown in chamber 92). Prior art SQUTD shields have only one chamber. The use of additional chamber, even though it adds complexity to the manufacturing process, is required to achieve the level of RF immunity needed for unshielded operation of the SQUTD instrument.

Figures 12(a) - 12(c) illustrate an exemplary SQUTD shield 90 including an outer housing 96 with a bore 97 for receiving an insert 93 having relieved portions 98, 99. When insert 93 is inserted into bore 97, each of relieved portions 98, 99 fits sealably within bore 97 to respectively define electromagnetically sealed chambers 91, 92.

A second bore 94 (for example, less than a tenth of the diameter of the shield) in insert 93 allows passage of electrical wires to connect between the SQUTD 91a in chamber 91 with the filter circuit 92a in chamber 92 without any electromagnetic leakage. A ground connection 95 is provided for the filter circuit 92a in chamber 92 so ground loop currents are now shielded from the SQUTD. This isolation, in addition to the symmetric electronics, fully eliminates any grounding issues in the apparatus.

In summary, a system and method are disclosed for effective implementation of a practical sub-pico Tesla magnetic field detector that is insensitive to RFI. While various embodiments have been shown and described, it will be understood that there is no intent to limit the invention by such disclosure, but rather, it is intended to cover many modifications and altemate constructions falling within the spirit and the scope of the invention, as defined in the appended claims. For example, the present invention should not be limited by specific hardware or type of filter circuit. Thus, one skilled in the art can envision using other forms of filter circuits (just as an example, a filter made up of superconducting striplines) having similar properties (for example, cut-off frequency and sharpness of characteristics).

Claims

CLAIMSWe claim:

1. In an apparatus for measuring a magnetic field comprising a superconducting quantum interference device (SQUID) inductively coupled to a gradiometer, a device for shielding the SQUTD from radio frequency interference (RFI) picked up through the gradiometer, the device including: a filter circuit having a resistor-capacitor (RC) combination interconnected to first and second terminals so that the filter circuit is electrically parallel to both an input coil of the SQUTD and the gradiometer, wherein the filter circuit is effective to shunt both magnetically-induced and electrically-induced components of RFI generated in the gradiometer away from the input coil.

2. The apparatus of claim 1, wherein the filter circuit includes: a first shunt resistor Rs connected between the first terminal and a third terminal; a second shunt resistor Rs connected between the second terminal and the third terminal; and a grounding capacitor C_g connected between the third terminal and a system ground.

3. The apparatus of claim 1, wherein the filter circuit includes: a first shunt resistor Rs connected between the first terminal and the second terminal; a first series grounding circuit including a first grounding resistor R_g and a first grounding capacitor C_g connected between the first terminal and a system ground; and a second series grounding circuit including a second grounding resistor R_g and a second grounding capacitor C_g connected between the second terminal and a system ground.

4. The apparatus of claim 1, wherein the filter circuit includes: a first series shunting circuit including a first shunting resistor Rs and a first shunting capacitor Cs connected between the first terminal and a third terminal; a second series shunting circuit including a second shunting resistor Rs and a second shunting capacitor Cs connected between the third terminal and the second terminal; and a grounding capacitor C_g connected between the third terminal and a system ground.

5. The apparatus of claim 1, wherein the filter circuit includes: a first series shunting circuit including a first shunting resistor Rs and a first shunting capacitor Cs connected between the first terminal and the second terminal terminal; a first series grounding circuit including a first grounding resistor R_g and a first grounding capacitor C_g connected between the first terminal and a system ground; and a second series grounding circuit including a second grounding resistor R_g and a second grounding capacitor C_g connected between the second terminal and a system ground.

6. The apparatus of claim 1, wherein the filter circuit includes: a first shunt resistor R_s connected between the first terminal and a third terminal; a second shunt resistor R_s connected between the second terminal and the third terminal; a third shunt resistor R connected between the first terminal and the second terminal; and a grounding capacitor C_g connected between the third terminal and a system ground.

7. In an apparatus for measuring a magnetic field comprising a superconducting quantum interference device (SQUTD) electrically coupled to a gradiometer, wherein the SQUTD comprises an insulator separating a SQUTD washer from an input coil at a predetermined distance t, the input coil being interconnected to the gradiometer, a method for reducing coupling of radio frequency interference (RFI) into the SQUID through the gradiometer by increasing the capacitive impedance Zc, between the input coil and the SQUTD washer, the method comprising the steps of: reducing a conductor width in the input coil in order to reduce a capacitance C, of the coil; and providing the coil with a number of turns N such that a stripline inductance of the input coil L_str,_p is negligible as compared to N *L_SQ, wherein L_SQ is an inductance of the SQUTD washer, such that an input coil inductance Li is approximately equal to N²*L_SQ; such that C, is decreased, and Zc, is increased, and the sensitivity S of the apparatus is unchanged, wherein S is inversely proportional to the sum of a gradiometer inductance L_g and input coil inductance L,.

8. The method of claim 7, wherein N exceeds 20.

9. The method of claim 9, wherein N exceeds 100.

10. The apparatus of claim 1, further including a shield for housing the SQUTD and the RC circuit so that the RC circuit is electromagnetically isolated from the SQUTD.

11. The apparatus of claim 10, wherein the shield comprises two electromagnetically isolated chambers each for housing one of the SQUTD and the RC circuit, wherein the two electromagnetically isolated chambers are interconnected by a third chamber having a diameter d.

12. The apparatus of claim 11, wherein the diameter d is less than 1/10 of an overall diameter ds_H of the shield.

13. The apparatus of claim 11, wherein the one electromagnetically isolated chamber for housing the RC circuit includes a grounding terminal.