CA2148961C - Linear alternating current interface for electronic meters - Google Patents
Linear alternating current interface for electronic metersInfo
- Publication number
- CA2148961C CA2148961C CA002148961A CA2148961A CA2148961C CA 2148961 C CA2148961 C CA 2148961C CA 002148961 A CA002148961 A CA 002148961A CA 2148961 A CA2148961 A CA 2148961A CA 2148961 C CA2148961 C CA 2148961C
- Authority
- CA
- Canada
- Prior art keywords
- input
- coil
- amplifier
- interface circuit
- transformer
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Expired - Fee Related
Links
Classifications
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R21/00—Arrangements for measuring electric power or power factor
- G01R21/133—Arrangements for measuring electric power or power factor by using digital technique
-
- G—PHYSICS
- G01—MEASURING; TESTING
- G01R—MEASURING ELECTRIC VARIABLES; MEASURING MAGNETIC VARIABLES
- G01R15/00—Details of measuring arrangements of the types provided for in groups G01R17/00 - G01R29/00, G01R33/00 - G01R33/26 or G01R35/00
- G01R15/14—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks
- G01R15/18—Adaptations providing voltage or current isolation, e.g. for high-voltage or high-current networks using inductive devices, e.g. transformers
Abstract
An interface circuit (10) for use with electronic metering equipment (E) to provide a linear output response to an AC or analog input. An air core transformer (12) has a first coil or winding (12a) connected to a load (L). An AC current ILOAD is produced by the load and is coupled to a secondary coil or winding (12b) of the transformer. The transformer has an air core rather than a ferromagnetic core so to have no saturable core. Because no load is drawn by transformer coil, the voltage across a terminal of the coil equals the EMF
induced in the coil The EMF, in turn, equals the mutual inductance of the coils multiplied by the rate of change of magnetic flux linkages over time. The output from the transformer is applied as an input to an operational-amplifier (16) which has a high input impedance. Further, the amplifier is a low drift amplifier which performs a linear amplification of the input signal provided thereto. In certain embodiments, a pair of similar amplifiers are used and the secondary winding of the transformer is a tapped winding so to accommodate both a low range and a separate high range of inputs. The output from the operational amplifier is supplied to an analog-to-digital converter (18) so a digital output is supplied to the metering equipment. If the tapped coil, dual amplifier arrangement is used, the resolution requirements of the converter are lower than if the single amplifier circuit configuration is used. Use of the interface circuit eliminates the DC
component of the sensed voltage and provides a linear response for the metered AC input to the measuring equipment.
induced in the coil The EMF, in turn, equals the mutual inductance of the coils multiplied by the rate of change of magnetic flux linkages over time. The output from the transformer is applied as an input to an operational-amplifier (16) which has a high input impedance. Further, the amplifier is a low drift amplifier which performs a linear amplification of the input signal provided thereto. In certain embodiments, a pair of similar amplifiers are used and the secondary winding of the transformer is a tapped winding so to accommodate both a low range and a separate high range of inputs. The output from the operational amplifier is supplied to an analog-to-digital converter (18) so a digital output is supplied to the metering equipment. If the tapped coil, dual amplifier arrangement is used, the resolution requirements of the converter are lower than if the single amplifier circuit configuration is used. Use of the interface circuit eliminates the DC
component of the sensed voltage and provides a linear response for the metered AC input to the measuring equipment.
Description
~? IL~8q6 ~
Background of the InYention This invention relates to electronic metering and, more pd~ ,ulal ly, to an alternating current (AC) interface circuit which provides a linear current response when connected to an AC load. The circuit is for use with electronic meters to simplify 5 operation of metering circuits. A method for ;,~1,l..,,..,l,,,~ such a circuit is also disclosed.
In Illea~u~ ,.,L systems for many, varied dlJpl;~,dliul~i in which AC loads are monitored, AC signals are to be measured to obtain relevant information. In such,I;r,.~ , it is known to use a ~dll~iUIIII~,. such as a step-down ferromagnetic core 0 ~.dll,rullll~,. tû convert a high level AC signal, which could damage the measuring equipment, to a lower level AC signal which can be measured to produce apprûpriate i,,r~.,,,,~l;l ,. for the user without damaging the monitoring/test equipment. A drawback with using the standard ~lallirullll~ typically available for this purpose is that they are physically large units, having non-linear ~ L ~ ala~,Lel;~;c~, and poor frequency 15 response. The non-linearity of their response greatly uullllJ~;cdL~ the operation of the measuring equipment since the equipment must employ other circuitry to manipulate the output signals from the Llall~i~ùllll~r and provide a measurable signal. That is, mr~n~ n circuits, or circuits which produce some type of linearity for the Llall~rolll~l output must be employed to develop a signal which is processed to provide the ~0 Illc~a,~ llL ;l~llllali~ . The above noted non-linearity results because the core of the Lldll~r~JIl.l~l becomes saturated. Also, at higher frequencies, the various impedance levels within the Ll dll~rm 1ll~.. become significant.
Accordingly, it would be helptul to be able to provide an interface betweerl thesystem being monitored and the test equipment which alleviates these problems so2s accurate Ill~d~u~ can be readily made using a simpler test configuration. In this regard, digital signal processor (DSP) chips are now available at low cost. DSP's are programmed, or ~ulu~dll~ ablc to provide a wide variety of signal processing functions.
As such, they can be readily incorporated in electronic metering equipment to process inputs to obtain any of a desired range of significant information which can be derived 30 ~rom the input. This is significant because it allows a user, if he can provide an âppropriate input for processing to greatly increase the level of control over a using system.
M~y 9,19i4 _3 _ .
Summnly of the Invention Among the several obJects of the present invention may be noted the provision ofan interface circuit for use with electronic metering equipment monitoring AC loads; the provision of an interface circuit to provide a linear response to an AC input thereby to 5 simplify making of a ~ n ~ IL, the provision of such an interface circuit to transform a complex input signal into a signal having no DC component and an AC component whose response is linear over a wide range of signal frequencies; the provision of such an interface circuit employing an air core transformer and a high-impedance, low driflt linear amplifier to produce the linear response; the provision of such an interface circuit by which lo the input to the amplifier is on the order of 5mv. for a load current of I amp, and aLJ~lw~ ly Iv. at a load current of 2ûO amps so that the response is not only linear, but is a low level input which is readily measured by the metering equipment without the risk of damage; the provision of such an interface circuit to also employ an analog~to-digital converter (ADC) for the circuit to provide a digital output signal to the measuring 15 equipment; the provision of an interface circuit to utili~e a tapped or dual pickup coil al~àll~ in an air core ~lallsfollll~l to improve the accuracy of IllCdS.ll~ llL~i by providing both a low range and a high range of values; the provision of such a tapped or dual coil àllall~ L which reduces the resolution required for any analog-to-digital (AID) conversions made as part of measuring a particular parameter so to increase 20 conversion speed of the A/D conversion performed; the provision of such an interface to enable highly accurate readings to be made by the test equipment; and, the provision of.
such an interface which is low cost and usable with current, state-of-the-art digital signal processing equipment already ;",~ in many digital devices. The present inventionfurther includes the provision of a method by which the mutual inductance of the coils are 25 determined so no load is drawn from the coils; the provision of such a method by which the electro-motive force (EMF) induced in the coils is a function of the mutual inductance of the transformer coils including the râte change of magnetic flux linkage over time; the provision of such a method by which flux linkage is proportional to the current regardless of the current magnitude; the provision of such a method by which the flux linkage is 30 linearly 1~l upu. Liùl~àl to the current; the provision of such a method by which the number of bits required of an A/D converter to perform UUII~ IUI~S is minimized to facilitate circuit speed and reduce converter cost; and, the provision of such a method by which a 5427.DOC
~lay9, 1994 ~_ ~ 2148961 simple, easy to use interface circuit is provided for use with state-of-the-art processing equipment. Also, the present invention enables a user to not only eliminate the DC
component of a complex input signal, but to also perform a Fourier transform of the resultant AC signal so that the base frequency of the AC component of the input signal, as well as the harmonic frequencies of the signal can be made available for processing to obtain information relating to the system from which the input is obtained. The present invention envisages use of digital signal processing devices by which Fourier transforms of the AC component of an AC input are readily obtained for further processing In accordance with the invention, generally stated, an interface circuit is for use 0 with electronic metering equipment to provide a linear output response to an AC signal developed across a load. An air core Llal~srul~ has a primary winding connected across a load An AC current signal is developed by the load and is coupled to a secondary winding of the ~LàllSru~ The ~lallarul~ has an air core rather than a r~l~u~l~a~ .ic core, the air core not being a saturable core. The output from the Llallarullll~l is applied as an input to an operational-amplifier (op-amp) having a high input impedance. The Llallaru~ el is designed to provide a linear response to a wide range of input signals applied to the primary winding so the output applied from the transformer to the op-amp is directly proportional to the input signal. The amplifier is a low drift ampli~ler which performs an amplification of the input signal provided thereto. In certain ~llLud;lll~llLa, a pair of similar amplifiers are used and the secondary winding of the transformer is a tapped winding. This allows the interface circuit to provide inputs to the amplifiers in a respective low range and high range. The output from the operational amplifier is supplied to an analog-to-digital converter so a digital output is supplied to the metering equipment. A method of I~ an interface circuit providing a linear response is also disclosed, as is a method of processing a complex input signal to eliminate the DC
component of the signal as well as produce harmonics of the signal for subsequent additional processing. Other objects and features will be in part apparent and in part pointed out hereinaf er.
Brief Description of t~le Drawings Fig. I is a schematic diagram of an interface circuit of the present invention for use with measuring equipment For measuring a digital signal input;
5427.DOC
M4y 9, 1994 S_ 21~8g61 Fig. 2 is a schematic diagram of an alternate ~mhol1im~nt of the interface for providing inputs to the measuring equipment in more than one data range;
_Fig. 3 is a graph It~ a~llLil~g both the current i(t) and EMF e(t) curves for aselected set of parameters and includes the filn~ml~nt~l frequency of the waveform, and 5 the third and fifth harmonics of the r;~."lA."~ IAI frequency;
Fig. 4 is a curve for a Discrete Fourier Transform of the curve of Fig. 3, the transform being for a waveform having a first frequency with the curve ,t,uleatllL;llg data from samples taken at a second and higher frequency;
Fig. 5A represents both a curve of the 1~ ,. .~IAI 11. . IIA1 frequency of the current curve 0 of Fig. 3, and a curve It~!Lta~llL;llg the fi~nr~Amrnt~l frequency when divided by a harmonic number and shifted by 90;
Fig. SB is a plot similar to Fig. SA but for the third harmonic, and Fig. 5C is a similar plot for the fifth harmonic;
Fig. 6 is an illustration of one method for ~ :r~ o mutual inductance between 15 the primary and secondary coils or windings of an air core [l~larul lll~,. used in the circuit;
Fig. 7 is an illustration of a second method of d~ "..;"i"~ the mutual intillctAn~P;
and, Fig. 8 is a diagram useful with the method of Fig. 7 for ~ t~rminino fiux linkages in the l~allarullll~l coil.
CUllta~Ul~ , reference characters indicate l.UIItalJUIIa;llg parts throughout the several views of the drawings. --Description of Preferred ~ml~ot~imPnt~
Referring to the drawings, an alternating current interface circuit of the pFesent invention for use in electronic metering equipment is indicated generally by reference 10 in Fig.
1~ It is a feature of the circuit. as described herein, to provide a linear response. Interface circuit 10 includes a coupling means 11 comprising a ~ arullll~l 12 having primary and secondary coils or windings 12a and 12b l-,apC.,~ y. Winding 12a has associated terminals 14a, 14b across which are connected a load L. A current ILo,~D is produced by this load. It will be understood that the load represents of a number of different types of loads which may simple or complex loads. The other ~lallarullll~l winding 12b has associated terminals 14c, 14d. Importantly, LlA~larullll~l 12 is an air core ~ransformer rather than a standard type transformer having a rt~lulll~ll~ ; core. Transformer winding s427.rJoc M~y9, ~994 21~8961 12b is coupled to the magnetic field generated by flow of the load current ILoAD through the Llal~rvl~ primary winding. When there is no load on this winding, the voltage across the winding terminals 14c, 14d ap~lu~illla~es the induced electromotive force (LMF) in the coil. This EMF, in turn, equals the mutual inductance Ms of the coil times 5 the negative rate of change of the magnetic flux linkage Y' over time. It will be understood that this flux linkage is proportional to the current i. Because no saturable material is used in the transformer; i.e., because it is an air core rather than a r~llul~ L;c core Llall~rullllel~ the flux linkage remains linearly proportional to current regardless of the magnitude of the current. If Lldl~srull~ l 12 were a r~l~ullla~ ,;h, core 0 Llall~rvl~ , the effects of saturation would have to be factored into the n~ tirln~ which follow and there would be a non-linearity which would make operation of the interface circuit impractical. In particular, it is of interest to eliminate the effects of the DC
component in the input, the DC portion of a signa] applied to a conventional LlallSrvllll~l having a ferromagnetic core helping produce the undesirable saturation and its effect on 15 response linearity.
To better understand operation of interface circuit 10, the relationship between the flux linkage and current is:
(1) ~ = k 1 i, where k is a IJ, U~)UI LiUl~dlity factor based upon a transformer's geometry and the 20 permeability of the material used in the transformer. The value of the EMF (eS) induced in the transformer is given as:
Background of the InYention This invention relates to electronic metering and, more pd~ ,ulal ly, to an alternating current (AC) interface circuit which provides a linear current response when connected to an AC load. The circuit is for use with electronic meters to simplify 5 operation of metering circuits. A method for ;,~1,l..,,..,l,,,~ such a circuit is also disclosed.
In Illea~u~ ,.,L systems for many, varied dlJpl;~,dliul~i in which AC loads are monitored, AC signals are to be measured to obtain relevant information. In such,I;r,.~ , it is known to use a ~dll~iUIIII~,. such as a step-down ferromagnetic core 0 ~.dll,rullll~,. tû convert a high level AC signal, which could damage the measuring equipment, to a lower level AC signal which can be measured to produce apprûpriate i,,r~.,,,,~l;l ,. for the user without damaging the monitoring/test equipment. A drawback with using the standard ~lallirullll~ typically available for this purpose is that they are physically large units, having non-linear ~ L ~ ala~,Lel;~;c~, and poor frequency 15 response. The non-linearity of their response greatly uullllJ~;cdL~ the operation of the measuring equipment since the equipment must employ other circuitry to manipulate the output signals from the Llall~i~ùllll~r and provide a measurable signal. That is, mr~n~ n circuits, or circuits which produce some type of linearity for the Llall~rolll~l output must be employed to develop a signal which is processed to provide the ~0 Illc~a,~ llL ;l~llllali~ . The above noted non-linearity results because the core of the Lldll~r~JIl.l~l becomes saturated. Also, at higher frequencies, the various impedance levels within the Ll dll~rm 1ll~.. become significant.
Accordingly, it would be helptul to be able to provide an interface betweerl thesystem being monitored and the test equipment which alleviates these problems so2s accurate Ill~d~u~ can be readily made using a simpler test configuration. In this regard, digital signal processor (DSP) chips are now available at low cost. DSP's are programmed, or ~ulu~dll~ ablc to provide a wide variety of signal processing functions.
As such, they can be readily incorporated in electronic metering equipment to process inputs to obtain any of a desired range of significant information which can be derived 30 ~rom the input. This is significant because it allows a user, if he can provide an âppropriate input for processing to greatly increase the level of control over a using system.
M~y 9,19i4 _3 _ .
Summnly of the Invention Among the several obJects of the present invention may be noted the provision ofan interface circuit for use with electronic metering equipment monitoring AC loads; the provision of an interface circuit to provide a linear response to an AC input thereby to 5 simplify making of a ~ n ~ IL, the provision of such an interface circuit to transform a complex input signal into a signal having no DC component and an AC component whose response is linear over a wide range of signal frequencies; the provision of such an interface circuit employing an air core transformer and a high-impedance, low driflt linear amplifier to produce the linear response; the provision of such an interface circuit by which lo the input to the amplifier is on the order of 5mv. for a load current of I amp, and aLJ~lw~ ly Iv. at a load current of 2ûO amps so that the response is not only linear, but is a low level input which is readily measured by the metering equipment without the risk of damage; the provision of such an interface circuit to also employ an analog~to-digital converter (ADC) for the circuit to provide a digital output signal to the measuring 15 equipment; the provision of an interface circuit to utili~e a tapped or dual pickup coil al~àll~ in an air core ~lallsfollll~l to improve the accuracy of IllCdS.ll~ llL~i by providing both a low range and a high range of values; the provision of such a tapped or dual coil àllall~ L which reduces the resolution required for any analog-to-digital (AID) conversions made as part of measuring a particular parameter so to increase 20 conversion speed of the A/D conversion performed; the provision of such an interface to enable highly accurate readings to be made by the test equipment; and, the provision of.
such an interface which is low cost and usable with current, state-of-the-art digital signal processing equipment already ;",~ in many digital devices. The present inventionfurther includes the provision of a method by which the mutual inductance of the coils are 25 determined so no load is drawn from the coils; the provision of such a method by which the electro-motive force (EMF) induced in the coils is a function of the mutual inductance of the transformer coils including the râte change of magnetic flux linkage over time; the provision of such a method by which flux linkage is proportional to the current regardless of the current magnitude; the provision of such a method by which the flux linkage is 30 linearly 1~l upu. Liùl~àl to the current; the provision of such a method by which the number of bits required of an A/D converter to perform UUII~ IUI~S is minimized to facilitate circuit speed and reduce converter cost; and, the provision of such a method by which a 5427.DOC
~lay9, 1994 ~_ ~ 2148961 simple, easy to use interface circuit is provided for use with state-of-the-art processing equipment. Also, the present invention enables a user to not only eliminate the DC
component of a complex input signal, but to also perform a Fourier transform of the resultant AC signal so that the base frequency of the AC component of the input signal, as well as the harmonic frequencies of the signal can be made available for processing to obtain information relating to the system from which the input is obtained. The present invention envisages use of digital signal processing devices by which Fourier transforms of the AC component of an AC input are readily obtained for further processing In accordance with the invention, generally stated, an interface circuit is for use 0 with electronic metering equipment to provide a linear output response to an AC signal developed across a load. An air core Llal~srul~ has a primary winding connected across a load An AC current signal is developed by the load and is coupled to a secondary winding of the ~LàllSru~ The ~lallarul~ has an air core rather than a r~l~u~l~a~ .ic core, the air core not being a saturable core. The output from the Llallarullll~l is applied as an input to an operational-amplifier (op-amp) having a high input impedance. The Llallaru~ el is designed to provide a linear response to a wide range of input signals applied to the primary winding so the output applied from the transformer to the op-amp is directly proportional to the input signal. The amplifier is a low drift ampli~ler which performs an amplification of the input signal provided thereto. In certain ~llLud;lll~llLa, a pair of similar amplifiers are used and the secondary winding of the transformer is a tapped winding. This allows the interface circuit to provide inputs to the amplifiers in a respective low range and high range. The output from the operational amplifier is supplied to an analog-to-digital converter so a digital output is supplied to the metering equipment. A method of I~ an interface circuit providing a linear response is also disclosed, as is a method of processing a complex input signal to eliminate the DC
component of the signal as well as produce harmonics of the signal for subsequent additional processing. Other objects and features will be in part apparent and in part pointed out hereinaf er.
Brief Description of t~le Drawings Fig. I is a schematic diagram of an interface circuit of the present invention for use with measuring equipment For measuring a digital signal input;
5427.DOC
M4y 9, 1994 S_ 21~8g61 Fig. 2 is a schematic diagram of an alternate ~mhol1im~nt of the interface for providing inputs to the measuring equipment in more than one data range;
_Fig. 3 is a graph It~ a~llLil~g both the current i(t) and EMF e(t) curves for aselected set of parameters and includes the filn~ml~nt~l frequency of the waveform, and 5 the third and fifth harmonics of the r;~."lA."~ IAI frequency;
Fig. 4 is a curve for a Discrete Fourier Transform of the curve of Fig. 3, the transform being for a waveform having a first frequency with the curve ,t,uleatllL;llg data from samples taken at a second and higher frequency;
Fig. 5A represents both a curve of the 1~ ,. .~IAI 11. . IIA1 frequency of the current curve 0 of Fig. 3, and a curve It~!Lta~llL;llg the fi~nr~Amrnt~l frequency when divided by a harmonic number and shifted by 90;
Fig. SB is a plot similar to Fig. SA but for the third harmonic, and Fig. 5C is a similar plot for the fifth harmonic;
Fig. 6 is an illustration of one method for ~ :r~ o mutual inductance between 15 the primary and secondary coils or windings of an air core [l~larul lll~,. used in the circuit;
Fig. 7 is an illustration of a second method of d~ "..;"i"~ the mutual intillctAn~P;
and, Fig. 8 is a diagram useful with the method of Fig. 7 for ~ t~rminino fiux linkages in the l~allarullll~l coil.
CUllta~Ul~ , reference characters indicate l.UIItalJUIIa;llg parts throughout the several views of the drawings. --Description of Preferred ~ml~ot~imPnt~
Referring to the drawings, an alternating current interface circuit of the pFesent invention for use in electronic metering equipment is indicated generally by reference 10 in Fig.
1~ It is a feature of the circuit. as described herein, to provide a linear response. Interface circuit 10 includes a coupling means 11 comprising a ~ arullll~l 12 having primary and secondary coils or windings 12a and 12b l-,apC.,~ y. Winding 12a has associated terminals 14a, 14b across which are connected a load L. A current ILo,~D is produced by this load. It will be understood that the load represents of a number of different types of loads which may simple or complex loads. The other ~lallarullll~l winding 12b has associated terminals 14c, 14d. Importantly, LlA~larullll~l 12 is an air core ~ransformer rather than a standard type transformer having a rt~lulll~ll~ ; core. Transformer winding s427.rJoc M~y9, ~994 21~8961 12b is coupled to the magnetic field generated by flow of the load current ILoAD through the Llal~rvl~ primary winding. When there is no load on this winding, the voltage across the winding terminals 14c, 14d ap~lu~illla~es the induced electromotive force (LMF) in the coil. This EMF, in turn, equals the mutual inductance Ms of the coil times 5 the negative rate of change of the magnetic flux linkage Y' over time. It will be understood that this flux linkage is proportional to the current i. Because no saturable material is used in the transformer; i.e., because it is an air core rather than a r~llul~ L;c core Llall~rullllel~ the flux linkage remains linearly proportional to current regardless of the magnitude of the current. If Lldl~srull~ l 12 were a r~l~ullla~ ,;h, core 0 Llall~rvl~ , the effects of saturation would have to be factored into the n~ tirln~ which follow and there would be a non-linearity which would make operation of the interface circuit impractical. In particular, it is of interest to eliminate the effects of the DC
component in the input, the DC portion of a signa] applied to a conventional LlallSrvllll~l having a ferromagnetic core helping produce the undesirable saturation and its effect on 15 response linearity.
To better understand operation of interface circuit 10, the relationship between the flux linkage and current is:
(1) ~ = k 1 i, where k is a IJ, U~)UI LiUl~dlity factor based upon a transformer's geometry and the 20 permeability of the material used in the transformer. The value of the EMF (eS) induced in the transformer is given as:
(2) eS = -d~//dt = -Ms di/dt.
While value es represents the voltage obtained from the transformer, it is important to obtain the current . This is done by performing an integration. If the above expression is 25 integrated, the value of current over time i(t) is found to be:
While value es represents the voltage obtained from the transformer, it is important to obtain the current . This is done by performing an integration. If the above expression is 25 integrated, the value of current over time i(t) is found to be:
(3) i(t) = -llMS I eS dt.
It is important to note that the current signal will now have no DC component, only an AC
signal l~ s~llLcd by a base frequency and harmonics of the base frequency.
For interface circuit 10, the output of winding 12b is applied to an operational30 amplifier (op-amp) 16. Op-amp 16 is supplied an operating voltage +V. A capacitor Cl is connected in parallel with the voltage source and the op-amp's supply voltage input terminal. The output of op-amp 16 (VOut) is provided to a voltage divider network 17 5417.DOC
M~y 9,1994 7 . . 2148961 .
comprising resistors R1, R2. The output from the network is supplied as an input to an analog-to-aigital conYerter (ADC) 18. The Yoltage diYider network is designed such that the input to the ADC is one-third, for example, the magnitude of the outout from the op-amp That is, Vin(ADC) = VoUt(Op amp)/3. This scaling factor of three is provided for reasons to be described hereinafter. The digital output from the ADC is provided to appropriate metering eciuipment E. It is important to understand that interface circuit l0 is usable exclusively with loads having AC currents. Arly drrect current (DC) constituent of a ioad current ir eliminated. By eliminating the DC component, the average net current should be 2ero. By providing a linear response to AC load currents, interface circuit 10 allows the metering eciuipment to be simpler than it would otherwise have to be. (~ circuits or ~ " ' ~D by which the metering e~iuipment will provide a linear response are not necessary when circuit 10 is used with the eciuipment.
The expression for a current i, including both its DC and AC components is a Fourier series which is set forth as:
It is important to note that the current signal will now have no DC component, only an AC
signal l~ s~llLcd by a base frequency and harmonics of the base frequency.
For interface circuit 10, the output of winding 12b is applied to an operational30 amplifier (op-amp) 16. Op-amp 16 is supplied an operating voltage +V. A capacitor Cl is connected in parallel with the voltage source and the op-amp's supply voltage input terminal. The output of op-amp 16 (VOut) is provided to a voltage divider network 17 5417.DOC
M~y 9,1994 7 . . 2148961 .
comprising resistors R1, R2. The output from the network is supplied as an input to an analog-to-aigital conYerter (ADC) 18. The Yoltage diYider network is designed such that the input to the ADC is one-third, for example, the magnitude of the outout from the op-amp That is, Vin(ADC) = VoUt(Op amp)/3. This scaling factor of three is provided for reasons to be described hereinafter. The digital output from the ADC is provided to appropriate metering eciuipment E. It is important to understand that interface circuit l0 is usable exclusively with loads having AC currents. Arly drrect current (DC) constituent of a ioad current ir eliminated. By eliminating the DC component, the average net current should be 2ero. By providing a linear response to AC load currents, interface circuit 10 allows the metering eciuipment to be simpler than it would otherwise have to be. (~ circuits or ~ " ' ~D by which the metering e~iuipment will provide a linear response are not necessary when circuit 10 is used with the eciuipment.
The expression for a current i, including both its DC and AC components is a Fourier series which is set forth as:
(4) i(t) = IdC + ilSin((i)lt + ~Pl) + i25in(~2t + ~Pl) + --+ in lsin(a)n lt + (,n-1) + inSin(~nt + (Pn) The EMF in a winding 12a or 12b equals the product of the coils' mutual inductance Ms and the deriYatiYe of current with respect to eime. A negative of the Yalue for EIviF is then:
(5) e = i1~1Mscos(cD1t + icl) + i2(~2MsC5(2t + lC2) + -+ in l~n 1Mscos(~n lt + lCn-1) + in)nMsCS(~nt + ICn).
Using the identity:
(c') cos(~t + :p + 7~/2) = -sin(o~t + ~p), the Yarious rrnctitll~ntc set forth in expression (4) aboYe can be identified. This is 2s done as follows:
a) for any kth term in equation (4), divide the term by k;
b) shift the result by a +90, and, c) multiply this result by -1.
When this is done, it will be found that the only part of expression (4) which is not l~,uY~lal:)le is the DC component. Now, Discrete Fourier Transforms (DFT's) can be used to find the respective harmonic component Yalues and phase angle of i.
~427.DOC
M~y9, 1994 21~8961 .
Referring to Fig 3, an exemplary current waveform for a current i(t) and a resultant EMF curve e(t) are depicted. The curve i(t) includes the fi~n-iAnn(-ntAI frequency as well as both the third harmonic and fifth harmonic l,UIII~/OllC.l~:i, The curve e(t) is derived in accordance with the steps a) and b) as set forth above. The respective curves 5 can be expressed as:
(7a) i(t) = lOOsin(~3t) + 25sin(3~t - 1.5) + 15sin(5~t - 0.3); and, (7b) e(t) = lOOcos( dt) + 75cos(30~t - 1.5) + 75cos(5~Dt - 0.3).
Fig. 4 represents a spectral distribution curve of the DFT of the waveform obtained from equation 7b. If the filn~lAnn~ntAI frequency is, for exannp]e 60Hz, and the lo sampling rate is 4320H~. The following table sets forth the harmonic number, relative strength, and phase angle as shown in the curve of Fig. 4.
Harmonic Strength Phase angle 0 0.00 0.000 1 100.00 - 0 000 2 0.00 - 0.970 3 75.00 - 1.500 4 0.00 - 0.374 5 75 .00 - 0.3 00 6 0.00 - 1.182 7 0.00 ~ - 0.886 8 0.00 - 0.537 9 0.00 0.377 0.00 - 0.902 11 0.00 1.393 12 0.00 0.464 13 0.00 - 1.029 14 0.00 - 0.327 0.00 0.866 16 0.00 1.035 17 0.00 0.081 18 0.00 1.570 ~4~7.r~oc May 9, 1994 .
19 0.00 - 1.399 20 0.00 - 0.555 Referring to Figs. 5A-SC, Fig. 5A illustrates both the filn~lrmPn~l frequency and shifted ~ Al frequency of the curve i(t) in Fig. 3. Fig. SB is a similar illustration 5 for the third harmonic of the i(t) curve; and, Fig. SC is a simi~ar illustration for the fifth harmonic. It will be appreciated that if Figs. SA-SC are superimposed upon each other, the current curve i(t) of Fig. 1 will be produced. Cu~ Llur~llLly~ the integration i(t) = -I/Ms I eS dt, as set forth in equation (3), has been ArcnmrlichPd by performing the following steps in 0 sequence:
a) dividing the current expression by (e/ o I)Ms;
b) carrying out a Discrete Fourier Transform on the result of the above step;
c) dividing the spectral strength of each harmonic by its harmonic number, i.e.,dividing the resulting expression for the third harmonic by three; and, d) performing a phase shift of the result of the above step, the phase shift being 1112 or 90.
For interface circuit 10 to be capable of determining the original current, it must be capable of 1) generating each harmonic of the filn~mPnts~l carrent; i.e., producing the curves of Figs. SA-SC; and, b) performing the sup~ ua;L;on of these curves to produce 20 the curve of Fig. 3.
Referring now to Fig. 6, for interface circuit 10 to be practical, the mutual inductance Ms between transformer windings 12a and 12b must be determined. The method of the present invention includes making this lPtPrmin~tinn. One way to determine mutual inductance is to assume a square coil Q which is comprised of a thin 25 wire. The length of the coil on each side is 1, and the surface area of the coil is equal to A.
The coil is positioned equidistantly between parallel, cylindrical conductors Yl, Y2.
The plane of the coil is assumed to coincide with that of the conductors. Each conductor has a radius rl, and the distance between the lnngitl~flinrl centerline of the conductors is a.
The distance from the lnngitllrinrl centerline of eacll conductor to the lnn~?itll~in~l 30 centerline of the coil is R. Furtl~er, the distance from the lon~itllr~inrl centerline of each conductûr to the adjacent edge of coil Q is a distance Rl . A current 11 flows in conductûr Yl, and a current I2 flows in conductor Y2. The currents fiow in opposite directions.
M~y9, 1994 -10- ;
Given these current conditions, the magnetic field H, and magnetic flux crossing the surface area of coil Q due to the flow of current Il, are:
(8a) H = rl/27~, and (8b) (~ = uo~A, S where ,Uio iS p~l"~al);l;~y Expression (8b) can also be written as:
(8c) ~p = J (,uoIII)/27~)RdR, where the limits of integration are from -Rl to Rl.
For the total current It (which is equal to currents Il + I2), the total magnetic fiux 0 ~Pt across the surface area of the coil is calculated according to the expression:-(9) ~Pt = ((llo(Il+I2)l)/27~)ln((a-Rl)lRl)) Next, assume that the number of turns of coil Q enclosing area A is N. For this condition, the total flux linkage is:
(lOa) yJ= ((~oNItl)/27r)ln((a~R1)/RI)) 15 The mutual inductance Ms can then be expressed as:
(lOb) Ms = yl/It, or (lOc) Ms= (IlONI)/27l)1n((a-RI)/Rl)).
Free space p~ dlFlriLy, in MKS units, is 4~10-7 ~ s/llleter. Substituting this value into equation (lOc) produces the expression:
Using the identity:
(c') cos(~t + :p + 7~/2) = -sin(o~t + ~p), the Yarious rrnctitll~ntc set forth in expression (4) aboYe can be identified. This is 2s done as follows:
a) for any kth term in equation (4), divide the term by k;
b) shift the result by a +90, and, c) multiply this result by -1.
When this is done, it will be found that the only part of expression (4) which is not l~,uY~lal:)le is the DC component. Now, Discrete Fourier Transforms (DFT's) can be used to find the respective harmonic component Yalues and phase angle of i.
~427.DOC
M~y9, 1994 21~8961 .
Referring to Fig 3, an exemplary current waveform for a current i(t) and a resultant EMF curve e(t) are depicted. The curve i(t) includes the fi~n-iAnn(-ntAI frequency as well as both the third harmonic and fifth harmonic l,UIII~/OllC.l~:i, The curve e(t) is derived in accordance with the steps a) and b) as set forth above. The respective curves 5 can be expressed as:
(7a) i(t) = lOOsin(~3t) + 25sin(3~t - 1.5) + 15sin(5~t - 0.3); and, (7b) e(t) = lOOcos( dt) + 75cos(30~t - 1.5) + 75cos(5~Dt - 0.3).
Fig. 4 represents a spectral distribution curve of the DFT of the waveform obtained from equation 7b. If the filn~lAnn~ntAI frequency is, for exannp]e 60Hz, and the lo sampling rate is 4320H~. The following table sets forth the harmonic number, relative strength, and phase angle as shown in the curve of Fig. 4.
Harmonic Strength Phase angle 0 0.00 0.000 1 100.00 - 0 000 2 0.00 - 0.970 3 75.00 - 1.500 4 0.00 - 0.374 5 75 .00 - 0.3 00 6 0.00 - 1.182 7 0.00 ~ - 0.886 8 0.00 - 0.537 9 0.00 0.377 0.00 - 0.902 11 0.00 1.393 12 0.00 0.464 13 0.00 - 1.029 14 0.00 - 0.327 0.00 0.866 16 0.00 1.035 17 0.00 0.081 18 0.00 1.570 ~4~7.r~oc May 9, 1994 .
19 0.00 - 1.399 20 0.00 - 0.555 Referring to Figs. 5A-SC, Fig. 5A illustrates both the filn~lrmPn~l frequency and shifted ~ Al frequency of the curve i(t) in Fig. 3. Fig. SB is a similar illustration 5 for the third harmonic of the i(t) curve; and, Fig. SC is a simi~ar illustration for the fifth harmonic. It will be appreciated that if Figs. SA-SC are superimposed upon each other, the current curve i(t) of Fig. 1 will be produced. Cu~ Llur~llLly~ the integration i(t) = -I/Ms I eS dt, as set forth in equation (3), has been ArcnmrlichPd by performing the following steps in 0 sequence:
a) dividing the current expression by (e/ o I)Ms;
b) carrying out a Discrete Fourier Transform on the result of the above step;
c) dividing the spectral strength of each harmonic by its harmonic number, i.e.,dividing the resulting expression for the third harmonic by three; and, d) performing a phase shift of the result of the above step, the phase shift being 1112 or 90.
For interface circuit 10 to be capable of determining the original current, it must be capable of 1) generating each harmonic of the filn~mPnts~l carrent; i.e., producing the curves of Figs. SA-SC; and, b) performing the sup~ ua;L;on of these curves to produce 20 the curve of Fig. 3.
Referring now to Fig. 6, for interface circuit 10 to be practical, the mutual inductance Ms between transformer windings 12a and 12b must be determined. The method of the present invention includes making this lPtPrmin~tinn. One way to determine mutual inductance is to assume a square coil Q which is comprised of a thin 25 wire. The length of the coil on each side is 1, and the surface area of the coil is equal to A.
The coil is positioned equidistantly between parallel, cylindrical conductors Yl, Y2.
The plane of the coil is assumed to coincide with that of the conductors. Each conductor has a radius rl, and the distance between the lnngitl~flinrl centerline of the conductors is a.
The distance from the lnngitllrinrl centerline of eacll conductor to the lnn~?itll~in~l 30 centerline of the coil is R. Furtl~er, the distance from the lon~itllr~inrl centerline of each conductûr to the adjacent edge of coil Q is a distance Rl . A current 11 flows in conductûr Yl, and a current I2 flows in conductor Y2. The currents fiow in opposite directions.
M~y9, 1994 -10- ;
Given these current conditions, the magnetic field H, and magnetic flux crossing the surface area of coil Q due to the flow of current Il, are:
(8a) H = rl/27~, and (8b) (~ = uo~A, S where ,Uio iS p~l"~al);l;~y Expression (8b) can also be written as:
(8c) ~p = J (,uoIII)/27~)RdR, where the limits of integration are from -Rl to Rl.
For the total current It (which is equal to currents Il + I2), the total magnetic fiux 0 ~Pt across the surface area of the coil is calculated according to the expression:-(9) ~Pt = ((llo(Il+I2)l)/27~)ln((a-Rl)lRl)) Next, assume that the number of turns of coil Q enclosing area A is N. For this condition, the total flux linkage is:
(lOa) yJ= ((~oNItl)/27r)ln((a~R1)/RI)) 15 The mutual inductance Ms can then be expressed as:
(lOb) Ms = yl/It, or (lOc) Ms= (IlONI)/27l)1n((a-RI)/Rl)).
Free space p~ dlFlriLy, in MKS units, is 4~10-7 ~ s/llleter. Substituting this value into equation (lOc) produces the expression:
(11) Ms=lN/5In((a-RI)/R~ H.
In this expression, l, a, and R1 are in meters. -As an example of how inductance is determined with the foregoing r~l~tion~hipc, assume N is 500 turns, a and l are each 5 cm., and R1 is 0.5 cm.. ~llhstitlltin~ these values into equation (Il) produces a calculated mutual inductance of diJl~U~ la~ly 11 2s ~ uhc iJ ici, e g., 10 986 11H Further, if the load current ILoAD is 200 amps (RMS) at 60Hz., the calculated induced EMF is approximately 1.~7 v. I.e.:
e = (377)(200)(~12)(l0 986~l0-6) = 1.1714 v, where The value 377 is equal to 27~ times 60Hz.
What has now been ~crmplich--rl is replacing of the integration required to convert from the value eS to the expression for i(t) without having to integrate the expression for eS As noted, integration, or, in accordance with the method ùf the invention, perfùrming the Fourier transform to produce the base or filn~1~m~nt~1 frequency 5427.DOC
May9, 1994 -Il-of the signal, as well as the harmoniGs, achieves the same result in filtering or the DC
component of the complex signal input. The steps required to execute the method can be performed using a digital signal processor or DSP The DSP chip is programmed, or can be programmed, to divide the current expres3ion by (e/~dl)Ms, performing the discrete 5 Fourier transform, dividing the spectral strength of each harmonic by its harmonic number, and performing the 90 phase shift ofthe result .
Referring to Figs. 7 and 8, rather than having coil Q positioned between conductors Yl, Y2, the coil could be positioned between parallel bars or current carrying ribbons B 1, B2. Again, the length of the coil on each side is 1, and the surface area of o the coil is equal to A. The heigllt of each bar is 2h, and the distance between the bars is g. If the abscissa or y axis of a graph coincides with one of the bars, and the ordinate or x axis bisects the bar so that the bar extends a distance h on each side of the x axis, a point P located in space at some point from the bar will have co-ordinates P(x,y). This is as shown in Fig. 8. The linear distance from point P to the nearest point of the bar is a 15 distance r1, and the linear distance to the farthest point is a distance r2. The angle between a line ~cpl~ellLill~ the distance rl and the horizontal is al, and that between a line It~lC:>Clliillg the distance r2 and the horizontal is an angle 2 For this geometric relationship, the magnetic vector potential Al in the axial direction, with a current I flowing through the bars, is:
In this expression, l, a, and R1 are in meters. -As an example of how inductance is determined with the foregoing r~l~tion~hipc, assume N is 500 turns, a and l are each 5 cm., and R1 is 0.5 cm.. ~llhstitlltin~ these values into equation (Il) produces a calculated mutual inductance of diJl~U~ la~ly 11 2s ~ uhc iJ ici, e g., 10 986 11H Further, if the load current ILoAD is 200 amps (RMS) at 60Hz., the calculated induced EMF is approximately 1.~7 v. I.e.:
e = (377)(200)(~12)(l0 986~l0-6) = 1.1714 v, where The value 377 is equal to 27~ times 60Hz.
What has now been ~crmplich--rl is replacing of the integration required to convert from the value eS to the expression for i(t) without having to integrate the expression for eS As noted, integration, or, in accordance with the method ùf the invention, perfùrming the Fourier transform to produce the base or filn~1~m~nt~1 frequency 5427.DOC
May9, 1994 -Il-of the signal, as well as the harmoniGs, achieves the same result in filtering or the DC
component of the complex signal input. The steps required to execute the method can be performed using a digital signal processor or DSP The DSP chip is programmed, or can be programmed, to divide the current expres3ion by (e/~dl)Ms, performing the discrete 5 Fourier transform, dividing the spectral strength of each harmonic by its harmonic number, and performing the 90 phase shift ofthe result .
Referring to Figs. 7 and 8, rather than having coil Q positioned between conductors Yl, Y2, the coil could be positioned between parallel bars or current carrying ribbons B 1, B2. Again, the length of the coil on each side is 1, and the surface area of o the coil is equal to A. The heigllt of each bar is 2h, and the distance between the bars is g. If the abscissa or y axis of a graph coincides with one of the bars, and the ordinate or x axis bisects the bar so that the bar extends a distance h on each side of the x axis, a point P located in space at some point from the bar will have co-ordinates P(x,y). This is as shown in Fig. 8. The linear distance from point P to the nearest point of the bar is a 15 distance r1, and the linear distance to the farthest point is a distance r2. The angle between a line ~cpl~ellLill~ the distance rl and the horizontal is al, and that between a line It~lC:>Clliillg the distance r2 and the horizontal is an angle 2 For this geometric relationship, the magnetic vector potential Al in the axial direction, with a current I flowing through the bars, is:
(12) Az =(~Lo/27c)(II2h)[(y - h)(ln rl/h) - (y + h)(ln r2/h) + x(a2 - al)].
In addition, the respective magnetic field vectors B~x and By are calculated as follows:
(13a) Bx = -(oAz/~y), or (13b) BX=-(,U~27~)(Il2h)ln r2/rl And, (13c) By=-(~Az/ox), or (13d) By = -(LLl2~)(V2h)(ol2 - al).
If coil Q is positioned as shown in Fig. 8; i. e., with its center at x =0, y =0, there is no contribution to the flux in the x direction, so Bx = 0. Further, the expression for the-component in the y direction can be reduced to (14) By= (LLoI/4h) - (,~LOI/21lh)arctan[x/h].
If coil Q fits snuggly between bars B 1, B2, then for one bar to carry the current I, the enclosed flux (,D can be calculated as:
54Z7.DOC
May9, 1994 -12-2~4~961 (15a) tp = J Byldx~ with the respective lower and upper limits of integration being 0 and a. Accordingly, (lSb) ç = (uOIla/4h) ~ oll/27~h) ¦ x*arctan x/h - h/2 In (1~ a2/h2) ¦ Oa.
ARer performing the integration, the preceding expression becomes;
(15c) (p = (1aOIla/4h) ~ OIU2~h)[a~arctan a/h - h/2 In (1+ a2/h2)].
Employing this relationship in the same manner as with the previous example, the mutual inductance Ms for a coil Q of N turns is:
(16) Ms = (uONla/4h) - (,uONla/2~h)arctan(a/h - (uoNI/47~)1n (1+ a2/h2).
Referring again to Fig. 1, with the coil design of L~ ru- ~,.el 12 in accordance with 0 either of the above described examples, op-amp 16 is, as noted, a high input impedance op-amp. Further, the op-amp is a low drift amplifier having linear operating Lics From the previous discussion, it will be understood that the voltage input Vin to op-amp 16 will range between, for example, 5.g5 mv. to 1.17 v. The lower voltage occurs at a load current of 1 amp, and the higher voltage at a load current of 200 amps.
For this wide range of input voltage values, the driR in the output voltage Vout is less than 1%. Op-amp 16 is, for example, a model LTI 101 precision, micropower instrumentation amplifier having a fixed gain of either 10 or 100. The overall gain error (Ge) of the ampliFler is L~ 04~/o maximum. Gain driR (Gdr) is on the order of 4 parts per million (ppm).
The input voltage to the amplifier has an offset (Vos) which is 1601aV. The amplifer further has an input bias current (Ib) of 8 nA., and the supply current to the amplifier is 105 ,uA.
For the circuit configuration of Flg. 1, the percentage oftotal error is a function of both a steady state offset error (ERoff)~ and driR error (ERdr). The steady state offset error is given by the expression:
(17) E~off= Ge + Vos, where Ge is the op-amp gain error. If the lowest input coil voltage is the 5.85 mv. Ievel discussed above, a worst case offset error (referenced to Vout) can be calculated to be less than _ 3.4 %. With appropriate calibration, this error can also be eliminated.
Next, the drift error ERd[(max), refererced to the input of the op-amp, can be dP~PrminPd. This is done as follows:
(18a) Vout(max) = Vin~Gdr, (18b) Vin = Vcoil(~ 1 A.) + Zcoil(Ib) + Vin(offset max.), s4l7.r~0c May 9, 1994 2148g61 .
where Zcoil is the coil impedance.
Given the above rf~i~ti-lnchirs and inserting the appropriate values, Vin is fo~md to be 5.88 mv. Further, Vout(max) is found to be 58.84 mv. ERdr(max) is now determined by the equation:
(18c) E~dr(max) = 1.0 - (10)(Vin))/Vout(max))i'100.
Using the respective values for Vin and Vout(max), the maximum drit`t error is calculated to be i 0.4C/~
The total output voltage range for op-amp 16 extends from 58.5 mV. at 1 amp, to 11.71 V. at 200 amps. For an ADC operation to be practical, the output from the op-amp is scaled down This scaling is provided by the voltage divider network 1~ shown in Fig.
1; and, as previously mentioned, the scaling factor is three. With the voltage divider network scaling down VOut(op-amp) by a factor 3, the input range of the voltagessupplied to ADC 18 ranges from 19.5 mV. to 3.9 V. If worst case accuracy is 1%, which occurs at a 3 amp load, the accuracy of the current channel is on the order of 0.5% If VOut(op-amp) at 3 amps is 58.5 mV., and the accuracy of the current channe~ is 0.5%, then the accuracy of the ADC is dlJLll u~ a~ely .29 mv. For an ADC 18 having a SV. full scale range, the resolution of the ADC is alulu~ dll~aL~ly I in 17000. Since 214 equals 16,384, and 215 equals 32,768, the resolution of the ADC should be 15 bits.
Referring to Fig. 2, an altemate i ' ' of the interface circuit of the present invention is indicated generally by reference 20. Circuit 20 includes a coupling means 21 comprising an air core transfor~ner 22 having respective windings æa, æb. Winding 22a hæ
respective terminals 24a, 24b, and a load L' is coMected to the transfommer across these windings.
There is a mutual inductance Ms between the windings; and, this inductance together with the other parameters required to design an air core transformer in accordance with the teachings of the present invention are as previously described. Next, circuit 20 includes a pair of operational amplifiers 26a, 26b which are also model number LT1101 op-amps. Each op-arnp has an associated capacitor C2, C3 connected in parallel with the voltage input to the op-amp.
One input to op-amp 26a is connected to a terminal 24c of winding 22b. .-Winding 22b is a tapped coil with the tap being connected to a llallsr~ l terminal 24d.
This terminal is connected to the similar input of op-amp 26b as the input to which terminal 24c is connected on op-amp 26a. A~so, the other input of each ~p-amp is , 54~7 DOC
~y 9~ ~994 ..
In addition, the respective magnetic field vectors B~x and By are calculated as follows:
(13a) Bx = -(oAz/~y), or (13b) BX=-(,U~27~)(Il2h)ln r2/rl And, (13c) By=-(~Az/ox), or (13d) By = -(LLl2~)(V2h)(ol2 - al).
If coil Q is positioned as shown in Fig. 8; i. e., with its center at x =0, y =0, there is no contribution to the flux in the x direction, so Bx = 0. Further, the expression for the-component in the y direction can be reduced to (14) By= (LLoI/4h) - (,~LOI/21lh)arctan[x/h].
If coil Q fits snuggly between bars B 1, B2, then for one bar to carry the current I, the enclosed flux (,D can be calculated as:
54Z7.DOC
May9, 1994 -12-2~4~961 (15a) tp = J Byldx~ with the respective lower and upper limits of integration being 0 and a. Accordingly, (lSb) ç = (uOIla/4h) ~ oll/27~h) ¦ x*arctan x/h - h/2 In (1~ a2/h2) ¦ Oa.
ARer performing the integration, the preceding expression becomes;
(15c) (p = (1aOIla/4h) ~ OIU2~h)[a~arctan a/h - h/2 In (1+ a2/h2)].
Employing this relationship in the same manner as with the previous example, the mutual inductance Ms for a coil Q of N turns is:
(16) Ms = (uONla/4h) - (,uONla/2~h)arctan(a/h - (uoNI/47~)1n (1+ a2/h2).
Referring again to Fig. 1, with the coil design of L~ ru- ~,.el 12 in accordance with 0 either of the above described examples, op-amp 16 is, as noted, a high input impedance op-amp. Further, the op-amp is a low drift amplifier having linear operating Lics From the previous discussion, it will be understood that the voltage input Vin to op-amp 16 will range between, for example, 5.g5 mv. to 1.17 v. The lower voltage occurs at a load current of 1 amp, and the higher voltage at a load current of 200 amps.
For this wide range of input voltage values, the driR in the output voltage Vout is less than 1%. Op-amp 16 is, for example, a model LTI 101 precision, micropower instrumentation amplifier having a fixed gain of either 10 or 100. The overall gain error (Ge) of the ampliFler is L~ 04~/o maximum. Gain driR (Gdr) is on the order of 4 parts per million (ppm).
The input voltage to the amplifier has an offset (Vos) which is 1601aV. The amplifer further has an input bias current (Ib) of 8 nA., and the supply current to the amplifier is 105 ,uA.
For the circuit configuration of Flg. 1, the percentage oftotal error is a function of both a steady state offset error (ERoff)~ and driR error (ERdr). The steady state offset error is given by the expression:
(17) E~off= Ge + Vos, where Ge is the op-amp gain error. If the lowest input coil voltage is the 5.85 mv. Ievel discussed above, a worst case offset error (referenced to Vout) can be calculated to be less than _ 3.4 %. With appropriate calibration, this error can also be eliminated.
Next, the drift error ERd[(max), refererced to the input of the op-amp, can be dP~PrminPd. This is done as follows:
(18a) Vout(max) = Vin~Gdr, (18b) Vin = Vcoil(~ 1 A.) + Zcoil(Ib) + Vin(offset max.), s4l7.r~0c May 9, 1994 2148g61 .
where Zcoil is the coil impedance.
Given the above rf~i~ti-lnchirs and inserting the appropriate values, Vin is fo~md to be 5.88 mv. Further, Vout(max) is found to be 58.84 mv. ERdr(max) is now determined by the equation:
(18c) E~dr(max) = 1.0 - (10)(Vin))/Vout(max))i'100.
Using the respective values for Vin and Vout(max), the maximum drit`t error is calculated to be i 0.4C/~
The total output voltage range for op-amp 16 extends from 58.5 mV. at 1 amp, to 11.71 V. at 200 amps. For an ADC operation to be practical, the output from the op-amp is scaled down This scaling is provided by the voltage divider network 1~ shown in Fig.
1; and, as previously mentioned, the scaling factor is three. With the voltage divider network scaling down VOut(op-amp) by a factor 3, the input range of the voltagessupplied to ADC 18 ranges from 19.5 mV. to 3.9 V. If worst case accuracy is 1%, which occurs at a 3 amp load, the accuracy of the current channel is on the order of 0.5% If VOut(op-amp) at 3 amps is 58.5 mV., and the accuracy of the current channe~ is 0.5%, then the accuracy of the ADC is dlJLll u~ a~ely .29 mv. For an ADC 18 having a SV. full scale range, the resolution of the ADC is alulu~ dll~aL~ly I in 17000. Since 214 equals 16,384, and 215 equals 32,768, the resolution of the ADC should be 15 bits.
Referring to Fig. 2, an altemate i ' ' of the interface circuit of the present invention is indicated generally by reference 20. Circuit 20 includes a coupling means 21 comprising an air core transfor~ner 22 having respective windings æa, æb. Winding 22a hæ
respective terminals 24a, 24b, and a load L' is coMected to the transfommer across these windings.
There is a mutual inductance Ms between the windings; and, this inductance together with the other parameters required to design an air core transformer in accordance with the teachings of the present invention are as previously described. Next, circuit 20 includes a pair of operational amplifiers 26a, 26b which are also model number LT1101 op-amps. Each op-arnp has an associated capacitor C2, C3 connected in parallel with the voltage input to the op-amp.
One input to op-amp 26a is connected to a terminal 24c of winding 22b. .-Winding 22b is a tapped coil with the tap being connected to a llallsr~ l terminal 24d.
This terminal is connected to the similar input of op-amp 26b as the input to which terminal 24c is connected on op-amp 26a. A~so, the other input of each ~p-amp is , 54~7 DOC
~y 9~ ~994 ..
-14- .
commonly connected to a terminal 24e which attaches to the other side of the winding.
Each section of winding 22b is optimized for a particular current range. As shown in Fig.
2, the lQwer portion 22c of winding 22b is for use with load currents of 60 amps, or less, for example. The other section 22d of the coil is for use with load currents of between 60 amps and 200 amps. It will be understood that the respective ranges can be changed by changing the location of the tap.
The output of both op-amps is supplied to an ADC 28. The output of op-amp 26a, the low range output, is supplied to a low range input of the ADC via a voltage divider network 27a comprising resistors R3, R4. The output of op-amp 26b is supplied o to a high range input of the ADC through a voltage divider network 27b comprising resistors RS, R6. As before, the voltage divider networks provide the scaling factor (3) for the reasons previously described. The ADC output is supplied to the measuring equipment E'. For this interface circuit cu,,rl~uldL;ull7 the accuracy required at 3 ampsl in the lower range, is 166.67 mv. If the accuracy of the current channel is again 0.5%, the calculated resolution is I in 6000. Since 212 ;5 4096, and 213 is 8192, a 13 bit converter is used. This is based on a full scale range which is again 5 V. The comparable calculation for the higher range is I in 853. Since 29 is 512, and 21 is 1024, a 10 bit converter would be used.
The advantage of the interface circuit 20 of Fig. 2 is that the tapped coil technique and dual amplifiers reduces the resolution of the AID conversion which is performed by the circuit. T~ of the circuit could require use of a multiple~er and an additional current channel. However, the reduction in resolution achieved by the circuit means a lower cost ADC can be used in the circuit and the conversion will be faster.
What has been described is a linear, alternating current interface for use with electronic metering equipment. The interface employs an air core transformer and a high-impedance, low drift linear amplifier which has, for cxample, an input of d,utJlu~dl~,dttly 5mv. for a load current of I amp, and dlJt~lu~dl~d~ly lv. at a load current of Z~0 amps.
Accordingly, the response is not only linear, but is a low level input readily measured by the metering equipment. The interface can also utilize a tapped or dual pickup coil ~Illallg~ i to improve the accuracy of measurements by providing a low range and high range of values. This tapped coil or dual coil arrangement reduces the resolution of any A/D conversions made as part of measuring a particular parameter. This increases the s427.roc M~y 9, 1994 .
conversion speed of for A/D conversion performed. Use of the interface facilitates readily obtainable, highly accurate readings The interface is a low cost interface usable with current, state-of-the-art digital signal processing equipment imrlr-mr-nt~-d in many digital devices. In accordance with the interface and method of the present invention, a user can 5 readily eliminate the DC component of a complex input signal, and perform a Fourier transform of the resultant AC signal to obtain a signal for processing which includes the base or firml:lmt~nt~l frequency of the AC component, as well as the harmonic frequencies of the signal. Performing the Fourier transform achieves the same result as performing an integration of a voltage signal but is done so in a manner by which extensive infr~rmrti~n is o obtained from the results of the operation.
In view of the foregoing, it will be seen that the several objects of the invention are achieved and other advantageous results are obtained.
As various changes could be made in the above constructions without departing from the scope of the invention, it is intended that all the matter contained in the above 15 description or shown in the a~ dlly;l~g drawings shall be interpreted as illustrative and not in a limiting sense.
s427.r~0c M~y 9, 1994
commonly connected to a terminal 24e which attaches to the other side of the winding.
Each section of winding 22b is optimized for a particular current range. As shown in Fig.
2, the lQwer portion 22c of winding 22b is for use with load currents of 60 amps, or less, for example. The other section 22d of the coil is for use with load currents of between 60 amps and 200 amps. It will be understood that the respective ranges can be changed by changing the location of the tap.
The output of both op-amps is supplied to an ADC 28. The output of op-amp 26a, the low range output, is supplied to a low range input of the ADC via a voltage divider network 27a comprising resistors R3, R4. The output of op-amp 26b is supplied o to a high range input of the ADC through a voltage divider network 27b comprising resistors RS, R6. As before, the voltage divider networks provide the scaling factor (3) for the reasons previously described. The ADC output is supplied to the measuring equipment E'. For this interface circuit cu,,rl~uldL;ull7 the accuracy required at 3 ampsl in the lower range, is 166.67 mv. If the accuracy of the current channel is again 0.5%, the calculated resolution is I in 6000. Since 212 ;5 4096, and 213 is 8192, a 13 bit converter is used. This is based on a full scale range which is again 5 V. The comparable calculation for the higher range is I in 853. Since 29 is 512, and 21 is 1024, a 10 bit converter would be used.
The advantage of the interface circuit 20 of Fig. 2 is that the tapped coil technique and dual amplifiers reduces the resolution of the AID conversion which is performed by the circuit. T~ of the circuit could require use of a multiple~er and an additional current channel. However, the reduction in resolution achieved by the circuit means a lower cost ADC can be used in the circuit and the conversion will be faster.
What has been described is a linear, alternating current interface for use with electronic metering equipment. The interface employs an air core transformer and a high-impedance, low drift linear amplifier which has, for cxample, an input of d,utJlu~dl~,dttly 5mv. for a load current of I amp, and dlJt~lu~dl~d~ly lv. at a load current of Z~0 amps.
Accordingly, the response is not only linear, but is a low level input readily measured by the metering equipment. The interface can also utilize a tapped or dual pickup coil ~Illallg~ i to improve the accuracy of measurements by providing a low range and high range of values. This tapped coil or dual coil arrangement reduces the resolution of any A/D conversions made as part of measuring a particular parameter. This increases the s427.roc M~y 9, 1994 .
conversion speed of for A/D conversion performed. Use of the interface facilitates readily obtainable, highly accurate readings The interface is a low cost interface usable with current, state-of-the-art digital signal processing equipment imrlr-mr-nt~-d in many digital devices. In accordance with the interface and method of the present invention, a user can 5 readily eliminate the DC component of a complex input signal, and perform a Fourier transform of the resultant AC signal to obtain a signal for processing which includes the base or firml:lmt~nt~l frequency of the AC component, as well as the harmonic frequencies of the signal. Performing the Fourier transform achieves the same result as performing an integration of a voltage signal but is done so in a manner by which extensive infr~rmrti~n is o obtained from the results of the operation.
In view of the foregoing, it will be seen that the several objects of the invention are achieved and other advantageous results are obtained.
As various changes could be made in the above constructions without departing from the scope of the invention, it is intended that all the matter contained in the above 15 description or shown in the a~ dlly;l~g drawings shall be interpreted as illustrative and not in a limiting sense.
s427.r~0c M~y 9, 1994
Claims (8)
1. An interface circuit for use with electronic metering equipment which meters alternating current (AC) parameters comprising:
means for coupling AC current flowing through a load to the electronic metering equipment used to perform the metering, said coupling means being a "no load" air core transformer having a primary coil to which the load is connected and a secondary coil whereby a voltage impressed across input terminals of the primary coil equals a voltage induced in the secondary coil, where the mutual inductance of the transformer is determined in accordance with the expression Ms = 1N/5 1n((a-R1)/R1)µH
and where a coil of the transformer winding is a thin wire, square coil equidistantly positioned between parallel, cylindrical conductors, the plane of the coil coinciding with that of the conductors with current flowing through one conductor in one direction and in the other conductor in the opposite direction, the coil having N number of turns and sides of length "1", the distance between the longitudinal centerline of the conductors being "a", and the distance from the longitudinal centerline of each conductor to the adjacent edge of the coil being R1;
amplifier means to which an AC signal developed by the secondary coils of said means for coupling is supplied, said AC signal being linearly proportional to the AC current flowing through the load, the amplifier means performing a linear amplification of the input provided thereto to produce an AC output signal; and, conversion means responsive to an output signal from the amplifier means for converting the AC signal from the amplifier means to a digital signal supplied to the electronic metering equipment used for metering purposes.
means for coupling AC current flowing through a load to the electronic metering equipment used to perform the metering, said coupling means being a "no load" air core transformer having a primary coil to which the load is connected and a secondary coil whereby a voltage impressed across input terminals of the primary coil equals a voltage induced in the secondary coil, where the mutual inductance of the transformer is determined in accordance with the expression Ms = 1N/5 1n((a-R1)/R1)µH
and where a coil of the transformer winding is a thin wire, square coil equidistantly positioned between parallel, cylindrical conductors, the plane of the coil coinciding with that of the conductors with current flowing through one conductor in one direction and in the other conductor in the opposite direction, the coil having N number of turns and sides of length "1", the distance between the longitudinal centerline of the conductors being "a", and the distance from the longitudinal centerline of each conductor to the adjacent edge of the coil being R1;
amplifier means to which an AC signal developed by the secondary coils of said means for coupling is supplied, said AC signal being linearly proportional to the AC current flowing through the load, the amplifier means performing a linear amplification of the input provided thereto to produce an AC output signal; and, conversion means responsive to an output signal from the amplifier means for converting the AC signal from the amplifier means to a digital signal supplied to the electronic metering equipment used for metering purposes.
2. The interface circuit of claim 1 wherein the amplifier means includes a low drift amplifier having a high input impedance.
3. The interface circuit of claim 1 wherein the amplifier means includes a second amplifier, the input signals to the amplifier means having a range of values and the input signals supplied to the respective amplifiers being separable into a first range corresponding to a low range of input values and a second range corresponding to an upper range of input values.
4. The interface circuit of claim 3 wherein the secondary coil of the transformer is a tapped coil whereby the coil is divided into a first section and a second section across each of an AC output signal is developed, the respective AC output signals being provided as an input to one of the respective amplifiers, the input to one of the amplifiers being a low range input and the input to the other amplifier being a high range input.
5. The interface circuit of claim 2 wherein an AC output signal of the amplifier is supplied as an input to an analog-to-digital converter to convert the AC signal to a digital output supplied to the electronic measuring equipment.
6. The interface circuit of claim 4 wherein an AC output signal of each respective amplifier is supplied as an input to an analog-to-digital converter to convert the respective low range and high range AC signals to the digital output signal supplied to electronic measuring equipment.
7. The interface circuit of claim 5 further including scaling means for scaling the output signal from the amplifier means supplied to the analog-to-digital converter.
8. The interface circuit of claim 6 further including scaling means for scaling the respective output signals from the amplifier means supplied to the analog-to-digital converter.
Applications Claiming Priority (2)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| US242,597 | 1994-05-13 | ||
| US08/242,597 US5696441A (en) | 1994-05-13 | 1994-05-13 | Linear alternating current interface for electronic meters |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CA2148961A1 CA2148961A1 (en) | 1995-11-14 |
| CA2148961C true CA2148961C (en) | 1999-04-27 |
Family
ID=22915432
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CA002148961A Expired - Fee Related CA2148961C (en) | 1994-05-13 | 1995-05-09 | Linear alternating current interface for electronic meters |
Country Status (2)
| Country | Link |
|---|---|
| US (1) | US5696441A (en) |
| CA (1) | CA2148961C (en) |
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-
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-
1995
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Also Published As
| Publication number | Publication date |
|---|---|
| CA2148961A1 (en) | 1995-11-14 |
| US5696441A (en) | 1997-12-09 |
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