US20050169020A1 - Power supply for use in an electronic energy meter - Google Patents
Power supply for use in an electronic energy meter Download PDFInfo
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- US20050169020A1 US20050169020A1 US11/045,645 US4564505A US2005169020A1 US 20050169020 A1 US20050169020 A1 US 20050169020A1 US 4564505 A US4564505 A US 4564505A US 2005169020 A1 US2005169020 A1 US 2005169020A1
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- voltage
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- primary winding
- power supply
- circuit
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/32—Means for protecting converters other than automatic disconnection
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
Description
- The present application is based on and claims priority to British Patent Application Serial No. 0402319.8 filed on Feb. 3, 2004.
- The present invention generally relates to the field of electronic electricity meters. More specifically, the present invention relates to a power supply for providing power to operate the electronic monitoring circuitry contained within an electronic electricity meter. An electricity metering system monitors power lines to derive polyphase input representations of voltage and current. Because electrical uses by different consumers can vary significantly, a typical utility providers require different meters for monitoring various primary voltages. Currently, available meters exist that utilize both electromechanical and electronic circuitry to monitor the voltage and current consumption.
- It has been recognized that a solid state electronic electricity meter provides a more dynamic device and a more accurate measurement of the energy consumption. However, the microprocessor-based monitoring circuitry used within electronic electricity meters requires the provision of one or more supply voltages to operate the monitoring circuitry. Internal power supplies that are capable of generating a relatively constant DC voltage from the three-phase AC line voltage being monitored have been used for this purpose. Since electric utility companies require meters for a variety of different primary AC line voltages, it has been necessary to provide power supplies that have individualized components to generate the microprocessor supply voltages from the variety of primary voltages.
- Various circuit designs, such as shown in U.S. Pat. No. 5,621,629, have been developed to provide a single meter that is capable of metering electrical energy associated with primary voltages that vary over a wide range. Although switching power supplies and voltage dividers are known for use in an electronic electricity meter, drawbacks exist with the currently available power supplies. Therefore, it is an object of the present invention to provide a power supply for an electronic electricity meter that addresses problems associated with currently available power supplies.
- The present invention involves a method and apparatus for providing a power supply for operating the electronic components contained with an electronic electricity meter, where the electronic electricity meter is capable of metering electrical energy consumption over a wide range of input voltage utilizing a single meter. The power supply circuit of the invention compensates for the wide range of input voltages and creates a generally constant DC supply voltage for use in powering the electronic circuitry within the electronic electricity meter.
- The power supply includes a transformer that has a primary winding that receives the line voltage and a secondary winding, where stored energy from the primary winding is discharged to the secondary winding. The secondary winding of the transformer creates and provides the output voltage for the power supply. A switch is connected to the primary winding of the transformer for selectively permitting and preventing the flow of current through the primary winding. When current is flowing through the primary winding, the core of the transformer is magnetized and no energy is flowing to the secondary winding. When the current path through the primary winding is broken, current is prevented from flowing through the primary winding and the stored energy in the primary winding is transferred to the secondary winding of the transformer to create an output voltage. The value of the output voltage is dictated by controlling the amount of time current is allowed to flow through the primary winding. The on and off time of the switch connected to the primary winding thus controls the output voltage at the secondary winding.
- A control circuit is coupled to the switch to provide a control signal to the switch to control the cyclic operation of the switch between the on and off positions. Preferably, the control circuit is a timer having on and off cycle times that are accurately controllable. Thus, the control signal from the control unit controls the cycle time of the switch, and thus the output voltage of the power supply.
- In one embodiment of the invention, an over voltage circuit is positioned to receive the half-wave rectified line voltage. The over voltage circuit compares the rectified line voltage to an upper voltage limit. If the value of the rectified line voltage exceeds the upper voltage limit, the over voltage circuit disables the generation of the control signal from the control unit to the switch. When the control signal is disabled, the current path through the primary winding of the transformer remains open such that current can no longer flow through the transformer. When current is prevented from flowing through the transformer, energy is not induced on the secondary winding of the transformer. Since energy is not being reflected from the secondary winding, no additional reflected voltage is present at the primary winding, thereby reducing the total voltage as seen by the switch of the power supply circuit. In this manner, the over voltage circuit limits the voltage present at the switch to protect the switch of the power supply circuit.
- In the preferred embodiment of the invention, the over voltage circuit includes hysteresis such that the over voltage circuit generates the over voltage signal when the DC bus voltage exceeds the upper voltage limit. Once the DC bus voltage falls below the upper voltage limit, the over voltage circuit will not terminate the over voltage signal until the DC bus voltage falls below an adjusted upper voltage limit, which is less than the upper voltage limit.
- In another embodiment of the invention, the power supply circuit includes a current limiting circuit that compares the current flowing through the primary winding of the transformer to an upper current limit. If the current flowing through the primary winding of the transformer exceeds the current limit, the current limiting circuit disables the generation of the control signal from the control unit, thus preventing further current flow through the primary winding of the transformer. Preferably, the current limiting circuit includes a timing circuit such that the operation of the transformer is disabled for a selected duration after the current returns below the current limit.
- The control circuit of the power supply circuit generates a control signal having a constant off time and a variable, controllable on-time. The on time of the control signal is inversely proportional to the value of the line voltage. In this manner, the control signal decreases the on time of the transformer for higher line voltages and increases on time when the line voltage is at a lower value. This feature allows the control circuit to more accurately maintain a constant output voltage for varying line voltages.
- The drawings illustrate the best mode presently contemplated of carrying out the invention.
- In the drawings:
-
FIG. 1 is a perspective view of an electronic three phase electricity meter including the power supply of the present invention; -
FIG. 2 is a block diagram of the power supply circuit of the present invention; -
FIG. 3 is a partial circuit diagram of the power supply circuit of the present invention; and -
FIG. 4 is a partial circuit diagram of the power supply circuit of the present invention. -
FIG. 1 illustrates a three-phaseelectronic electricity meter 10 constructed in accordance with the present invention. Theelectricity meter 10 includes an enclosed meter housing comprised of acover member 12 mounted to abase member 14. Thecover member 12 includes a generallyclear face surface 16 that allows adigital display 18 to be read from the exterior of theelectricity meter 10. Thecover member 12 andbase member 14 are joined to each other in a conventional manner such that thebase member 14 and thecover member 16 define a sealed, enclosed meter housing. The meter housing prevents moisture and other environmental contaminants from reaching the internal circuitry contained within the three-phaseelectronic electricity meter 10. - In the present invention, an operating and measurement circuit is contained within the meter housing that operates to measure the energy consumption and control the
digital display 18. The specific details of the measurement circuit will not be described in detail, since the measurement circuitry forms no part of the present invention. However, it should be understood that the measurement circuitry contained within the meter housing includes electronic components, including a current monitoring circuitry and processor, that require a constant DC voltage to operate. As can be seen inFIG. 1 , theelectricity meter 10 includes a plurality ofblades 20 that provide a point of connection between theelectronic electricity meter 10 of the present invention and the supply of electrical energy being monitored. - Referring now to
FIG. 2 , thereshown is apower supply circuit 22 for use in the electronic electricity meter. Thepower supply circuit 22 generally receives a three-phaseAC line voltage 24 and converts the AC line voltage to a constantDC output voltage 26 that is used to power the internal operating circuitry contained within the electronic electricity meter. In the embodiment of the invention illustrated, theoutput voltage 26 is a constant 12 volts DC. The constant 12 voltDC output voltage 26 can be stepped up or down to any other DC voltage required by the internal circuitry within the electronic electricity meter in a known manner. - As described previously, the
AC line voltage 24 received at the electronic electricity meter is typically in the range of between 96 and 630 volts AC. Thepower supply circuit 22 of the present invention converts the variableinput line voltage 24 into a constant 12 voltDC output voltage 26. - As illustrated in
FIG. 2 , the threephase line voltage 24 is half-wave rectified by arectifier circuit 28 to create aDC bus voltage 30. TheDC bus voltage 30 is supplied to amain power converter 32. In the embodiment of the invention shown inFIG. 2 , themain power converter 32 is a transformer having a primary winding 34 and a secondary winding 36. Further details of the primary and secondary windings of themain power converter 32 will be described in greater detail below. - As shown in
FIG. 2 , aswitch 38 is connected to the primary winding 34 of thepower converter 32. Theswitch 38 is selectively operable to permit and prevent the flow of current through the primary winding 34. Theswitch 38 is operable in response to a control signal generated by thecontrol circuit 40. When theswitch 38 is turned on, a connection is made to ground through the primary winding 34 and current flows through the primary winding to energize the magnetic core of the primary winding 34. When theswitch 38 is in the off position, the connection of the primary winding 34 to ground is broken and the stored magnetic energy from the primary winding 34 of the transformer is transferred to the secondary winding 36. The secondary winding 36 of the transformer is connected to a smoothing circuit to generate theoutput voltage 26. The value of theoutput voltage 26 can be regulated by controlling the ratio of the on and off time of theswitch 38. As shown, the operation of theswitch 38 between the on and off positions is controlled by a control signal from thecontrol circuit 40. - The
power supply circuit 22 includes avoltage feedback circuit 42 positioned between theoutput voltage 26 and thecontrol circuit 40. Thevoltage feedback circuit 42 compares theoutput voltage 26 to a desired reference voltage and generates a signal to inhibit the operation of thecontrol circuit 40 if the output voltage exceeds the desired voltage. If theoutput voltage 26 falls below the desired reference voltage, thecontrol unit 40 is able to generate the control signal to the switch. If theoutput voltage 28 exceeds the desired voltage, the voltage feedback circuit inhibits the generation of the control signal until the output voltage falls below the desired voltage. - In the embodiment of the invention illustrated in
FIG. 2 , thepower supply circuit 22 also includes a current limitingcircuit 44. The current limitingcircuit 44 is particularly desirable to prevent damage to thepower supply circuit 22 in the event of a secondary side failure of thepower converter 32. In general, thecurrent limit circuit 44 monitors the current in the primary winding 34 of thepower converter 32. If the current in the primary winding 34 exceeds an upper current limit, the current limitingcircuit 44 inhibits the generation of the control signal from thecontrol circuit 40, which interrupts the operation of thepower converter 32 for an interruption period. The current limitingcircuit 44 is particularly important at the start up, when the transformer primary current becomes continuous while the output voltage is rising. - In addition to limiting the current through the
transformer 32, thepower supply circuit 22 of the present invention also includes an overvoltage protection circuit 46. In the embodiment of the invention illustrated inFIG. 2 , theswitch 38 has a maximum voltage rating. As an example, theswitch 38 in the present invention is a transistor rated to 1,000 volts. During the discharge of the primary winding 34 to the secondary winding 36, an additional 200 volts of reflected secondary voltage may appear at the primary winding 34. Thus, during discharge of the primary winding, theswitch 38 sees the combination of theDC bus voltage 30 and the reflected voltage from the secondary winding 36. If theswitch 38 is rated to 1,000 volts, this allows for safe operation up to a DC bus voltage of approximately 800 volts. - At the high end of the power supply's input range, the peak
DC bus voltage 30 will reach approximately 814 volts. To prevent damage to theswitch 38, the overvoltage circuit 46 prevents operation of thepower converter 32 for input voltages above an upper voltage limit. In the embodiment of the invention, the overvoltage circuit 46 operates to prevent operation of thepower converter 32 for input voltages above 700 volts. When thepower converter 32 is interrupted, theswitch 38 sees only theDC bus voltage 30. - As illustrated in
FIG. 2 , the overvoltage circuit 46 monitors the voltage on theDC bus 30 and interrupts the generation of the control signal from thecontrol circuit 40 when the bus voltage exceeds the upper voltage. When the bus voltage exceeds the upper voltage, current flow through the primary winding 34 is prevented. - The
power supply circuit 22 includes astartup circuit 48 that is connected to theDC bus voltage 30. Thestartup circuit 48 includes a current source that charges a capacitor. Once the capacitor reaches an under voltage threshold, thestartup circuit 48 signal thecontrol circuit 40 to begin operation of thepower converter 32. - As can be understood by the above description, the
power supply circuit 22 of the present invention disables the operation of thepower converter 32 when the rectified line voltage exceeds an upper voltage limit. Further, thepower supply circuit 22 of the present invention provides a current limiting circuit to prevent damage to thepower switch 38. - Referring now to
FIGS. 3 and 4 , thereshown is the detailed circuit schematic that embodies the block diagram ofFIG. 2 . Although a detailed circuit schematic is shown inFIGS. 3 and 4 to provide a preferred embodiment of thepower supply circuit 22, it should be understood that other embodiments of the invention can be created while operating within the scope of the present invention. - As shown in
FIG. 3 , the three-phase AC line voltages 24 are connected to the input of therectifier circuit 28. Therectifier circuit 28 includesdiodes capacitors line voltage 24. A pair ofcapacitors rectifier circuit 28 creates a half-wave rectified DC bus voltage atline 30. As described previously, the three-phaseAC line voltage 24 may vary between 96 and 630 volts AC. - As illustrated in
FIG. 3 , theDC bus voltage 30 is applied to the primary winding 34 of the transformer 33, which functions as the power converter. In the embodiment of the invention illustrated, the primary winding 34 includes afirst coil 66 and asecond coil 68 connected in series. The secondary winding 36 of the transformer 33 also includes afirst coil 70 and asecond coil 72 connected in parallel. - In the embodiment of the invention shown, the
main power switch 38 is a transistor positioned between the DC bus voltage and ground. When themain power switch 38 is turned on, a current path is created through diode 74,transistor 73 andresistors transistor 73 is turned on and a current path is created, magnetic energy builds in the primary winding 34 of the transformer 33. - The
power switch 38 receives a control signal alongline 82.Line 82 is coupled to the base of thetransistors transistor 73 through theresistors Line 82 is also coupled to theoutput pin 84 of thetiming control circuit 40 shown inFIG. 4 . In the embodiment of the invention illustrated, thetiming control circuit 40 is a conventional 555 timer that generates a periodic control signal that oscillates between zero and five volts atoutput pin 84. The control signal has a pre-set off time and an on time that is controlled by an input to the 555 timer. The output atpin 84 is coupled to alevel shifting circuit 86 that converts the five volt control signal from thecontrol circuit 40 to a level more suitable for driving thetransistor 73 that forms theswitch 38. Thelevel shifting circuit 86 is a generally conventional circuit, the details of which do not form part of the present invention. - Referring back to
FIG. 3 , when the signal online 82 turns theswitch 38 on, the primary winding 34 is charged. When the signal online 82 turns theswitch 38 off, the current path through theswitch 38 is interrupted. When the current path is interrupted, the energy stored in the primary winding 34 of the transformer 33 is transferred to thesecondary windings 36. The transferred energy flows through the diode 88 and into the pair ofparallel capacitors point 94. As described previously, the on and off times for theswitch 38 are regulated by the control signal from thecontrol circuit 40 such that theoutput voltage 26 is maintained at approximately 12 volts DC. - During the transfer of energy from the primary winding 34 to the secondary winding 36 when the
switch 38 is off, the primary winding 34 of the transformer 33 sees a reflected secondary voltage. During normal operating conditions, the reflected voltage is approximately 200 volts. Any additional energy stored in the primary leakage inductance of the transformer 33 is dissipated in the snubber circuit formed bydiodes switch 38, theswitch 38 will be exposed to the sum of the DC bus voltage present atline 30, which may range up to approximately 800 volts, plus up to an additional 224 volts of reflected voltage from the secondary winding 36. - In the embodiment of the invention illustrated, the
transistor 73 that forms theswitch 38 is available rated up to approximately 1,000 volts. As can be understood by the above description, theswitch 38 may be subjected to up to 1,024 volts during peak voltage values and peak reflected voltage from the secondary winding 36. As will be described below, an over voltage circuit is utilized as part of the power supply circuit of the present invention to limit the voltage that appears at theswitch 38. - In
FIG. 3 , theresistors transistor 73 and the primary inductance of the transformer. - Referring now to
FIG. 4 , thetiming control circuit 40 is configured to produce an output wave form atpin 84 that has a constant off time and an on time that is inversely proportional to the voltage on theDC bus 30. Thus, as the DC bus voltage increases, the on time of the control signal decreases and the amount of time current flows though the primary winding decreases. Likewise, if the voltage at the DC bus decreases, the on time of the control signal increases. In this manner, the control signal functions to maintain a generally constant DC output voltage over a variable AC line voltage range. - The voltage at the
DC bus 30 is fed to thecontrol circuit 40 fromline 104. The DC bus voltage is fed through aresistor network 106 totransistor 108. Thetransistor 108 has itsbase 110 connected to a five volt reference voltage atline 112. Thetransistor 108 is connected tocapacitor 114 and controls the charging time ofcapacitor 114. Adiode 116 provides a maximum on-time clamp for thetiming control circuit 40. In the embodiment of the invention illustrated, thediode 116 provides a maximum on-time clamp of approximately 6 μs - As illustrated in
FIG. 4 ,circuit 118 is connected to the 12 volt output voltage and generates the five volt reference signal online 112. The five volt reference signal is used throughout the power supply circuit in the manner to be described below. - As can be understood from the combination of
FIGS. 3 and 4 , theoutput voltage 26 is applied alongline 120 to thevoltage feedback circuit 42. Thevoltage feedback circuit 42 includes acomparator 122 that compares the output voltage atline 120 to a reference voltage created at 124 by the combination ofresistors line 120 is fed through a resistor dividernetwork including resistors resistor 126 is selected to be 9,100 ohms and theresistor 130 is selected to be 2,400 ohms. In order to reduce the noise susceptibility, approximately 200 mV of hysteresis is added to thecomparator 122. To provide the desired hysteresis, afeedback resistor 134 is included in the circuit. Anoutput resistor 136 is provided at the output of thecomparator 122. - When the output voltage at
line 120 is below the desired output voltage, thecomparator 122 generates a low signal at its output, which is received at thetransistor 138.Transistor 138 is coupled to thereset pin 140 of thecontrol circuit 40 throughdiode 139. During times at which the output voltage atline 120 is below the desired output voltage, thecontrol circuit 40 is able generate the control signal to theswitch 38 to activate the transformer 33. - If the output voltage at
line 120 is above the desired voltage, thecomparator 122 outputs a high value to thetransistor 138, which is received at the gate of the transistor. As illustrated, the source oftransistor 138 receives the control signal present at theoutput pin 84 of thecontrol circuit 40. When the control signal onpin 84 goes low, thetransistor 138 pulls thereset pin 140 low through thediode 139. When thereset pin 140 is low, the output onpin 84 of the control circuit is held low and theswitch 38 is held open such that current can no longer flow through the primary winding 34. - Once the output voltage falls below the desired voltage, the output of the
comparator 122 goes low and the control circuit can operate to generate the control signal onpin 84. The use of thevoltage feedback circuit 42 allows control over an exceedingly large range of line and load conditions without the associated problems of very small or large duty cycles. This is important since that the circuit of the present invention does not include any bulk capacitants on the high voltage DC rail and the transistor must be able to run over the entire line cycle. - Referring back to
FIG. 3 , it has been previously described that the preferredmain power switch 38 istransistor 73 rated up to 1,000 volts. Since an additional 200 volts of reflected secondary voltage may be seen by theswitch 38 in combination with theDC bus voltage 30 of up to 800 volts, an over voltage disablecircuit 46 is provided. In accordance with the preferred embodiment of the invention, to prevent damage to theswitch 38, the transformer 33 is prevented from transferring power from theprimary coil 34 to thesecondary coil 36 for voltages present at the DC bus of over 700 volts. The 700 volt upper voltage limit can be modified depending on the rating of thetransistor 73. When the transformer 33 is not running, theswitch 38 only sees theDC bus voltage 30. - The
DC bus voltage 30 is fed through a voltage divider, including a series ofresistors 142 andresistor 132, to theinput pin 144 of acomparator 146 of the overvoltage circuit 46, as shown inFIG. 4 . Thesecond input pin 148 of thecomparator 146 is connected to the reference voltage present online 124. As can be understood, theresistor network 142 andresistor 132 are selected such that the voltage at thepin 144 will exceed the reference voltage atline 124 when the DC line voltage exceeds 700 volts. If a different upper voltage limit is desired, the values of the resistors in the resistor divider network can be modified, as is well known. - When the DC bus voltage is below 700 volts, the
comparator 146 outputs a low value that is received at thetransistor 150 through theresistor 151. The low value at thetransistor 150 maintains thetransistor 150 in the off state, which enables the operation of thetiming control circuit 40 and the generation of the control signal onoutput pin 84. - When the DC bus voltage exceeds 700 volts, the
comparator 146 outputs a high signal to thetransistor 150, which is received at the gate of the transistor. As illustrated, the source oftransistor 150 receives the control signal present at theoutput pin 84 of thecontrol circuit 40. When the control signal onpin 84 goes low, thetransistor 150 pulls thereset pin 140 low through thediode 139. When thereset pin 140 is low, the output of the control circuit is held low and theswitch 38 is held open such that current can no longer flow through the primary winding 34 of the transformer. - When the
output pin 84 is disabled, the transformer is also disabled which results in thepower switch 38 only seeing the DC bus voltage and not the reflected voltage from the secondary winding 36. Thecomparator 146 includes afeedback resistor 153 that is used to introduce hysteresis into the overvoltage circuit 46. In the embodiment of the invention illustrated, the resistor values are selected such that the operation of the transformer is initially inhibited when the DC bus voltage exceeds 695 volts. The introduction of hysteresis into the circuit allows the transformer to only be reactivated when the DC bus voltage falls beneath an adjusted upper voltage limit or 679 volts. The inclusion of the hysteresis into the circuit ensures that the overvoltage protection circuit 46 initially interrupts operation when the DC bus voltage approaches 700 volts and continues to suspend operation until the DC bus voltage falls to an acceptable level further below the 700 volt maximum. - Once the DC bus voltage falls below the 700 volt upper voltage limit, the output of the
comparator 146 goes low and the control circuit can operate to generate the control signal onpin 84. - In addition to including an over voltage disable circuit, the
power supply circuit 22 of the present invention includes a current limitingcircuit 44. The current limitingcircuit 44 includes aninput 152. Theinput 152 senses the current flowing through the primary winding of the transformer, as represented by the voltage across theseries resistors FIG. 3 ). The current flowing through the series of resistors is the same current flowing through the primary winding 34 of the transformer 33. - The voltage at
input 152 is fed throughresistor 164 to inputpin 154 of thecomparator 156. Thesecond pin 158 is fed by thereference voltage 112 after passing through a voltage divider consisting ofresistors input pin 154 exceeds the upper current limit set by theresistors comparator 156 outputs a low signal to the base oftransistor 166. When the base oftransistor 166 is low,reset pin 140 of thecontrol circuit 40 is immediately pulled low to prevent the generation of the control signal atpin 84. When the control signal is no longer present, the operation of the transformer 33 is prevented. - As the base of the
transistor 166 is pulled low, thecapacitor 168 is discharged. Once the sensed current through the transformer falls below the upper current limit, thecomparator 156 again outputs a high signal to the base oftransistor 166. However, thereset pin 140 of thecontrol circuit 40 does not go high until thecapacitor 168 is charged. Thus, the operation of the transformer 33 is interrupted for a pre-selected period determined bycapacitor 168 andresistor 170 even after the value of the current falls below the upper current limit. - Referring again to
FIG. 4 , the power supply circuit of the present invention also includes the start-upcircuit 48. The start upcircuit 48 includes current source formed by thetransistors transistors resistor 178 anddiode 180 to thecapacitor 182. The voltage across thecapacitor 182 is fed throughresistor 184 to pin 186 of theunder voltage comparator 188.Pin 190 of thecomparator 188 receives a reference voltage defined by a voltagedivider including resistor voltage comparator 188 includes afeedback resistor 194 andgrounding resistor 196. The resistors are selected such that the comparator outputs a high signal at approximately 15 volts and is turned off when the voltage across thecapacitor 182 drops to approximately 8 volts. When thecomparator 188 turns off, the under voltage lock out is released and the current source provided by theseries transistors - In the specific embodiment of the invention shown in the circuit diagrams of
FIGS. 3 and 4 , the specific values for many of the circuit elements are not shown since the values for these components are a matter of design choice as can be recognized by those skilled in the art. Further, although the specific design configurations are shown for the various operating components of the power supply circuit, it should be understood that other circuit designs can be utilized while operating within the scope of the present invention.
Claims (20)
Applications Claiming Priority (2)
Application Number | Priority Date | Filing Date | Title |
---|---|---|---|
GBGB0402319.8A GB0402319D0 (en) | 2004-02-03 | 2004-02-03 | Wide range power supply for polyphase electricity meter |
GB0402319.8 | 2004-02-03 |
Publications (2)
Publication Number | Publication Date |
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US20050169020A1 true US20050169020A1 (en) | 2005-08-04 |
US7359221B2 US7359221B2 (en) | 2008-04-15 |
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Family Applications (1)
Application Number | Title | Priority Date | Filing Date |
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US11/045,645 Expired - Fee Related US7359221B2 (en) | 2004-02-03 | 2005-01-28 | Power supply for use in an electronic energy meter |
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US (1) | US7359221B2 (en) |
CA (1) | CA2557328C (en) |
GB (1) | GB0402319D0 (en) |
MX (1) | MXPA06009968A (en) |
WO (1) | WO2005076451A1 (en) |
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US9989568B2 (en) | 2014-04-07 | 2018-06-05 | TSTM, Inc. | Self-contained electrical meter arrangement with isolated electrical meter power supply |
US9824809B2 (en) | 2014-04-07 | 2017-11-21 | TSTM, Inc. | Modular transformer system |
US9766271B2 (en) | 2014-04-07 | 2017-09-19 | TSTM, Inc. | Transformer-rated electrical meter arrangement with isolated electrical meter power supply |
RU180905U1 (en) * | 2017-12-08 | 2018-06-29 | Акционерное общество "Радио и Микроэлектроника" | ELECTRIC ENERGY METER CURRENT CIRCUIT |
Citations (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US3666994A (en) * | 1970-06-18 | 1972-05-30 | Westinghouse Electric Corp | Overcurrent protective device |
US4210947A (en) * | 1977-10-06 | 1980-07-01 | Sony Corporation | Protective circuit for a switching regulator |
US5621629A (en) * | 1992-02-21 | 1997-04-15 | Abb Power T&D Company Inc. | Switching power supply for use in an electronic energy meter having a wide range of input voltages |
US5673184A (en) * | 1994-09-01 | 1997-09-30 | Deutsche Thomson-Brandt Gmbh | Switch mode power supply circuit with increased power factor for mains |
US5694304A (en) * | 1995-02-03 | 1997-12-02 | Ericsson Raynet Corporation | High efficiency resonant switching converters |
US5708572A (en) * | 1993-11-03 | 1998-01-13 | Braun Aktiengesellschaft | Switched-mode power supply |
US5973941A (en) * | 1997-07-17 | 1999-10-26 | Schlumberger Industries, S.A. | Electricity meter with a switching mode transformer power supply circuit |
US6351398B1 (en) * | 1999-09-24 | 2002-02-26 | Power Integrations, Inc. | Method and apparatus providing a multi-function terminal for a power supply controller |
US6980443B2 (en) * | 2003-04-10 | 2005-12-27 | Mitsumi Electric Co., Ltd. | Switching type AC adapter circuit with a latch protection circuit |
-
2004
- 2004-02-03 GB GBGB0402319.8A patent/GB0402319D0/en not_active Ceased
-
2005
- 2005-01-28 WO PCT/US2005/003345 patent/WO2005076451A1/en active Application Filing
- 2005-01-28 US US11/045,645 patent/US7359221B2/en not_active Expired - Fee Related
- 2005-01-28 MX MXPA06009968A patent/MXPA06009968A/en active IP Right Grant
- 2005-01-28 CA CA2557328A patent/CA2557328C/en active Active
Patent Citations (9)
Publication number | Priority date | Publication date | Assignee | Title |
---|---|---|---|---|
US3666994A (en) * | 1970-06-18 | 1972-05-30 | Westinghouse Electric Corp | Overcurrent protective device |
US4210947A (en) * | 1977-10-06 | 1980-07-01 | Sony Corporation | Protective circuit for a switching regulator |
US5621629A (en) * | 1992-02-21 | 1997-04-15 | Abb Power T&D Company Inc. | Switching power supply for use in an electronic energy meter having a wide range of input voltages |
US5708572A (en) * | 1993-11-03 | 1998-01-13 | Braun Aktiengesellschaft | Switched-mode power supply |
US5673184A (en) * | 1994-09-01 | 1997-09-30 | Deutsche Thomson-Brandt Gmbh | Switch mode power supply circuit with increased power factor for mains |
US5694304A (en) * | 1995-02-03 | 1997-12-02 | Ericsson Raynet Corporation | High efficiency resonant switching converters |
US5973941A (en) * | 1997-07-17 | 1999-10-26 | Schlumberger Industries, S.A. | Electricity meter with a switching mode transformer power supply circuit |
US6351398B1 (en) * | 1999-09-24 | 2002-02-26 | Power Integrations, Inc. | Method and apparatus providing a multi-function terminal for a power supply controller |
US6980443B2 (en) * | 2003-04-10 | 2005-12-27 | Mitsumi Electric Co., Ltd. | Switching type AC adapter circuit with a latch protection circuit |
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US20080002318A1 (en) * | 2006-06-30 | 2008-01-03 | Silicon Laboratories, Inc. | Voltage protection system and method for a powered device |
US7609494B2 (en) * | 2006-06-30 | 2009-10-27 | Silicon Laboratories, Inc. | Voltage protection system and method for a powered device |
US7847536B2 (en) | 2006-08-31 | 2010-12-07 | Itron, Inc. | Hall sensor with temperature drift control |
US8312103B2 (en) | 2006-08-31 | 2012-11-13 | Itron, Inc. | Periodic balanced communication node and server assignment |
US8299778B2 (en) | 2006-08-31 | 2012-10-30 | Itron, Inc. | Hall sensor with temperature drift control |
US8024724B2 (en) | 2006-08-31 | 2011-09-20 | Itron, Inc. | Firmware download |
US20080088296A1 (en) * | 2006-09-05 | 2008-04-17 | Makinson David N | Load side voltage sensing for AMI metrology |
US8049642B2 (en) | 2006-09-05 | 2011-11-01 | Itron, Inc. | Load side voltage sensing for AMI metrology |
US8138944B2 (en) | 2006-09-15 | 2012-03-20 | Itron, Inc. | Home area networking (HAN) with handheld for diagnostics |
US8284107B2 (en) | 2006-09-15 | 2012-10-09 | Itron, Inc. | RF local area network antenna design |
US7826398B2 (en) | 2006-09-15 | 2010-11-02 | Itron, Inc. | Broadcast acknowledgement in a network |
US7827268B2 (en) | 2006-09-15 | 2010-11-02 | Itron, Inc. | Number of sons management in a cell network |
US7843834B2 (en) | 2006-09-15 | 2010-11-30 | Itron, Inc. | Use of minimal propagation delay path to optimize a mesh network |
US7843391B2 (en) | 2006-09-15 | 2010-11-30 | Itron, Inc. | RF local area network antenna design |
US9354083B2 (en) | 2006-09-15 | 2016-05-31 | Itron, Inc. | Home area networking (HAN) with low power considerations for battery devices |
US7848362B2 (en) | 2006-09-15 | 2010-12-07 | Itron, Inc. | Real time clock distribution and recovery |
US7929916B2 (en) | 2006-09-15 | 2011-04-19 | Itron, Inc. | Embedded RF environmental evaluation tool to gauge RF transceivers performance need |
US7965758B2 (en) | 2006-09-15 | 2011-06-21 | Itron, Inc. | Cell isolation through quasi-orthogonal sequences in a frequency hopping network |
US7986718B2 (en) | 2006-09-15 | 2011-07-26 | Itron, Inc. | Discovery phase in a frequency hopping network |
US7756030B2 (en) | 2006-09-15 | 2010-07-13 | Itron, Inc. | Downlink routing mechanism |
US8045537B2 (en) | 2006-09-15 | 2011-10-25 | Itron, Inc. | Traffic load control in a mesh network |
US7756078B2 (en) | 2006-09-15 | 2010-07-13 | Itron, Inc. | Cell size management |
US8055461B2 (en) | 2006-09-15 | 2011-11-08 | Itron, Inc. | Distributing metering responses for load balancing an AMR network |
US8054821B2 (en) | 2006-09-15 | 2011-11-08 | Itron, Inc. | Beacon requests and RS bit resolving circular routes |
US8059011B2 (en) | 2006-09-15 | 2011-11-15 | Itron, Inc. | Outage notification system |
US8059009B2 (en) | 2006-09-15 | 2011-11-15 | Itron, Inc. | Uplink routing without routing table |
US20080095075A1 (en) * | 2006-09-15 | 2008-04-24 | Fabrice Monier | Discovery phase in a frequency hopping network |
US8212687B2 (en) | 2006-09-15 | 2012-07-03 | Itron, Inc. | Load side voltage sensing for AMI metrology |
US8270910B2 (en) | 2006-09-15 | 2012-09-18 | Itron, Inc. | Embedded RF environmental evaluation tool to gauge RF transceivers performance need |
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US8462015B2 (en) | 2006-09-15 | 2013-06-11 | Itron, Inc. | Real time clock distribution and recovery |
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Also Published As
Publication number | Publication date |
---|---|
US7359221B2 (en) | 2008-04-15 |
CA2557328A1 (en) | 2005-08-18 |
WO2005076451A1 (en) | 2005-08-18 |
GB0402319D0 (en) | 2004-03-10 |
CA2557328C (en) | 2013-09-24 |
MXPA06009968A (en) | 2007-03-07 |
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